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16 pages, 1912 KiB  
Article
Inhibition of Ionic Currents by Fluoxetine in Vestibular Calyces in Different Epithelial Loci
by Nesrien M. M. Mohamed, Frances L. Meredith and Katherine J. Rennie
Int. J. Mol. Sci. 2024, 25(16), 8801; https://doi.org/10.3390/ijms25168801 - 13 Aug 2024
Viewed by 203
Abstract
Previous studies have suggested a role for selective serotonin reuptake inhibitors (SSRIs) such as fluoxetine (Prozac®) in the treatment of dizziness and inner ear vestibular dysfunction. The potential mechanism of action within the vestibular system remains unclear; however, fluoxetine has been [...] Read more.
Previous studies have suggested a role for selective serotonin reuptake inhibitors (SSRIs) such as fluoxetine (Prozac®) in the treatment of dizziness and inner ear vestibular dysfunction. The potential mechanism of action within the vestibular system remains unclear; however, fluoxetine has been reported to block certain types of K+ channel in other systems. Here, we investigated the direct actions of fluoxetine on membrane currents in presynaptic hair cells and postsynaptic calyx afferents of the gerbil peripheral vestibular system using whole cell patch clamp recordings in crista slices. We explored differences in K+ currents in peripheral zone (PZ) and central zone (CZ) calyces of the crista and their response to fluoxetine application. Outward K+ currents in PZ calyces showed greater inactivation at depolarized membrane potentials compared to CZ calyces. The application of 100 μM fluoxetine notably reduced K+ currents in calyx terminals within both zones of the crista, and the remaining currents exhibited distinct traits. In PZ cells, fluoxetine inhibited a non-inactivating K+ current and revealed a rapidly activating and inactivating K+ current, which was sensitive to blocking by 4-aminopyridine. This was in contrast to CZ calyces, where low-voltage-activated and non-inactivating K+ currents persisted following application of 100 μM fluoxetine. Additionally, marked inhibition of transient inward Na+ currents by fluoxetine was observed in calyces from both crista zones. Different concentrations of fluoxetine were tested, and the EC50 values were found to be 40 µM and 32 µM for K+ and Na+ currents, respectively. In contrast, 100 μM fluoxetine had no impact on voltage-dependent K+ currents in mechanosensory type I and type II vestibular hair cells. In summary, micromolar concentrations of fluoxetine are expected to strongly reduce both Na+ and K+ conductance in afferent neurons of the peripheral vestibular system in vivo. This would lead to inhibition of action potential firing in vestibular sensory neurons and has therapeutic implications for disorders of balance. Full article
(This article belongs to the Special Issue Modulation of Ion Channels)
Show Figures

Figure 1

Figure 1
<p>K<sup>+</sup> conductances differ between PZ and CZ calyces in crista slices. (<b>A</b>) Representative K<sup>+</sup> currents in PZ (left, P26, male) and CZ (right, P24, male) calyces in response to a depolarizing step following a hyperpolarization. The calyces were held at −80 mV, stepped to −130 mV, and then to +20 mV for 40 ms (voltage protocol is shown below). Dashed line in this and subsequent figures indicates zero current (0 pA). I<sub>pk</sub> and I<sub>ss</sub> represent current measurements at peak and end of the 40 ms pulse, respectively, and were used to assess K<sup>+</sup> current inactivation. The scale bar applies to both PZ and CZ current recordings. CZ calyx shows a small low-voltage activated current (IK<sub>LV</sub>) that is active at the holding membrane potential of −80 mV and deactivates on stepping to the hyperpolarized potential. (<b>B</b>) Extent of K<sup>+</sup> current inactivation is compared for the calyces from different zones. Each symbol indicates the percentage of inactivation measured for individual calyces from PZ and CZ. Median inactivation (line in box plot) was 29.1% in PZ calyces (<span class="html-italic">n</span> = 31), significantly greater than the value of 9.4% in CZ calyces (<span class="html-italic">n</span> = 27; <span class="html-italic">p</span> &lt; 0.001, Mann–Whitney rank-sum Test) **. (<b>C</b>) Input resistance values are shown for PZ and CZ calyces. Median resistance in PZ calyces (<span class="html-italic">n</span> = 31) was 446.2 MΩ, which was significantly higher than the value of 245.6 MΩ in CZ calyces (<span class="html-italic">n</span> = 27; <span class="html-italic">p</span> = 0.03, Mann–Whitney rank-sum test) *.</p>
Full article ">Figure 2
<p>Effect of fluoxetine on K<sup>+</sup> currents in PZ and CZ calyces. K<sup>+</sup> currents were recorded in response to the standard voltage step to +20 mV in control conditions (black traces) and in response to 100 μM fluoxetine (red traces). (<b>A</b>) In a PZ calyx (left, P26, female), 100 μM fluoxetine reduced outward K<sup>+</sup> current and revealed a rapidly activating, rapidly inactivating I<sub>K</sub>. In a CZ calyx (right, P28, female), fluoxetine also blocked a substantial component of outward I<sub>K</sub>; however, the remaining current did not inactivate. (<b>B</b>) Isolated calyx recording (female, P21, unknown zone) shows control, fluoxetine, and partial recovery of outward K<sup>+</sup> current after prolonged washing with control solution (&gt;16 min). (<b>C</b>) Fluoxetine at 100 μM blocked 50.1% of I<sub>pk</sub> and 57.3% of I<sub>ss</sub> in 12 PZ calyces, while in 5 CZ calyces, it blocked 56.4% of I<sub>pk</sub> and 56.8% of I<sub>ss.</sub> Each symbol indicates the percentage of blocked outward I<sub>K</sub> for individual calyces from PZ and CZ at I<sub>pk</sub> and I<sub>ss.</sub> Bars indicate mean ± SD.</p>
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<p>Combined effect of fluoxetine and 4-aminopyridine (4-AP) in PZ calyces. (<b>A</b>) Outward K<sup>+</sup> current recorded from a PZ calyx (P23, female) in response to a range of voltage steps. From a holding potential of −80 mV, the membrane was stepped to −130 mV, and then stepped from −90 mV to +20 mV in 10-mV incrementing steps. Voltage protocol is shown below the control current (left panel). A rapid transient inward Na<sup>+</sup> current (I<sub>Na</sub>) is seen at voltage steps between −60 mV and +10 mV. Currents in 100 μM fluoxetine are shown in the middle panel. Fluoxetine reduced outward I<sub>K</sub>, revealing a rapidly activating, rapidly inactivating K<sup>+</sup> current at depolarized steps. Subsequently, a combination of 100 μM fluoxetine and 1 mM 4-aminopyridine (4-AP) resulted in complete block of the outward K<sup>+</sup> current (right panel). (<b>B</b>) Impact of fluoxetine and fluoxetine/4-AP on the currents at the voltage step to +20 mV are shown. Control current (black), current following perfusion with 100 μM fluoxetine (green), and current following addition of 100 μM fluoxetine and 1 mM 4-AP (red) are shown. The fluoxetine-sensitive current (pink) and current blocked by 100 μM fluoxetine/1 mM 4-AP (blue) are also shown. As indicated, fluoxetine and 4-AP combined blocked almost all outward I<sub>K</sub>. (<b>C</b>) Current-voltage (I–V) plot illustrates the peak current measured over voltage steps for control (filled circles), fluoxetine (open circles), and fluoxetine/4-AP conditions (filled triangles). (<b>D</b>) Mean percentage of remaining current measured at +20 mV voltage step for PZ calyces (<span class="html-italic">n</span> = 3) was 54.7% after fluoxetine perfusion and 17.4% after combined perfusion with fluoxetine and 4-AP.</p>
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<p>Fluoxetine (100 μM) eliminates transient Na<sup>+</sup> currents in PZ and CZ calyx terminals. (<b>A</b>) Control I<sub>Na</sub> (black traces) recorded at test potential steps to −40 mV following a pre-pulse to −130 mV in a PZ calyx (P23, female) and CZ calyx (P26 male). Perfusion of 100 μM fluoxetine inhibited transient inward Na<sup>+</sup> currents (I<sub>Na</sub>) in both calyces as indicated by red traces. (<b>B</b>) Box plot demonstrates the impact of 100 μM fluoxetine on peak I<sub>Na</sub> (control, black symbols) in a total of 13 cells (5 PZ calyces, 4 CZ calyces, and 4 dissociated cells) at a test step to −40 mV. Application of 100 μM fluoxetine (red symbols) effectively eliminated I<sub>Na</sub>. Median values of I<sub>Na</sub> are shown in box plots, the control condition is significantly different after the application of 100 μM fluoxetine (<span class="html-italic">n</span> = 13; **** <span class="html-italic">p</span> &lt; 0.0001, Wilcoxon signed-rank test).</p>
Full article ">Figure 5
<p>Dose dependence of blockage of K<sup>+</sup> and Na<sup>+</sup> currents by fluoxetine. (<b>A</b>) Superimposed outward K<sup>+</sup> current recordings obtained from a CZ calyx (P30, male) in response to increasing concentrations of fluoxetine. Currents at the voltage step to +20 mV are shown. The control recording is depicted in black, while recordings for 25 μM, 33 μM, 50 μM, and 100 μM fluoxetine are shown in red, green, blue, and gray, respectively. (<b>B</b>) IV plot shows peak outward currents between −50 and +20 mV for control and increasing fluoxetine concentrations for the same cell shown in A. (<b>C</b>) Dose response for fluoxetine on K<sup>+</sup> currents using various concentrations (<span class="html-italic">n</span> = 4 cells for PZ and 4 cells for CZ). The EC<sub>50</sub>, representing the concentration of fluoxetine that induces 50% of the maximum effect, was determined to be 40.1 μM (Hill coefficient −5.0). Hexagons represent mean ± SD and crosses represent individual data points. (<b>D</b>) Inward Na<sup>+</sup> current recordings obtained from a CZ calyx (same as (<b>A</b>)) at the voltage step of −40 mV are superimposed for control (black trace), while those for 33 μM, 50 μM, and 100 μM fluoxetine are shown in green, blue, and gray, respectively. (<b>E</b>) Dose–response inhibitory effect of fluoxetine on inward Na<sup>+</sup> currents. Hexagons represent mean ± SD and crosses represent individual data points (<span class="html-italic">n</span> = 4 cells for PZ and 4 cells for CZ at different concentrations). EC<sub>50</sub> value for Na<sup>+</sup> currents is 32.1 µM (Hill coefficient −2.6).</p>
Full article ">Figure 5 Cont.
<p>Dose dependence of blockage of K<sup>+</sup> and Na<sup>+</sup> currents by fluoxetine. (<b>A</b>) Superimposed outward K<sup>+</sup> current recordings obtained from a CZ calyx (P30, male) in response to increasing concentrations of fluoxetine. Currents at the voltage step to +20 mV are shown. The control recording is depicted in black, while recordings for 25 μM, 33 μM, 50 μM, and 100 μM fluoxetine are shown in red, green, blue, and gray, respectively. (<b>B</b>) IV plot shows peak outward currents between −50 and +20 mV for control and increasing fluoxetine concentrations for the same cell shown in A. (<b>C</b>) Dose response for fluoxetine on K<sup>+</sup> currents using various concentrations (<span class="html-italic">n</span> = 4 cells for PZ and 4 cells for CZ). The EC<sub>50</sub>, representing the concentration of fluoxetine that induces 50% of the maximum effect, was determined to be 40.1 μM (Hill coefficient −5.0). Hexagons represent mean ± SD and crosses represent individual data points. (<b>D</b>) Inward Na<sup>+</sup> current recordings obtained from a CZ calyx (same as (<b>A</b>)) at the voltage step of −40 mV are superimposed for control (black trace), while those for 33 μM, 50 μM, and 100 μM fluoxetine are shown in green, blue, and gray, respectively. (<b>E</b>) Dose–response inhibitory effect of fluoxetine on inward Na<sup>+</sup> currents. Hexagons represent mean ± SD and crosses represent individual data points (<span class="html-italic">n</span> = 4 cells for PZ and 4 cells for CZ at different concentrations). EC<sub>50</sub> value for Na<sup>+</sup> currents is 32.1 µM (Hill coefficient −2.6).</p>
Full article ">Figure 6
<p>Fluoxetine does not block I<sub>K</sub> in type I and type II hair cells. (<b>A</b>) K<sup>+</sup> current recorded from a type I hair cell in crista slice (PZ, P22, male). Currents for control (black) and in Fluoxetine (red) are shown for the voltage step to +20 mV (voltage protocol is shown below). Application of 100 μM fluoxetine had little effect on current. (<b>B</b>) Currents recorded from a type II hair cell in crista slice (PZ, P22, female) at voltage steps to +20 mV in control (black) and 100 μM fluoxetine (red). (<b>C</b>) The mean peak outward K<sup>+</sup> currents measured at +20 mV voltage step for type I hair cells. Bars indicate mean ± SD (<span class="html-italic">n</span> = 7, <span class="html-italic">t</span> = −0.2, <span class="html-italic">p</span> = 0.8, paired <span class="html-italic">t</span>-test). (<b>D</b>) Box plots represent the median peak outward K<sup>+</sup> currents measured at +20 mV voltage step for type II hair cells before and after 100 μM fluoxetine perfusion (<span class="html-italic">n</span> = 4, <span class="html-italic">p</span> = 0.8, Mann–Whitney rank-sum Test).</p>
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14 pages, 6491 KiB  
Article
Effect of Synthetic Vitreous Fiber Exposure on TMEM16A Channels in a Xenopus laevis Oocyte Model
by Martina Zangari, Giuliano Zabucchi, Martina Conti, Paola Lorenzon, Violetta Borelli, Andrew Constanti, Francesco Dellisanti, Sara Leone, Lisa Vaccari and Annalisa Bernareggi
Int. J. Mol. Sci. 2024, 25(16), 8661; https://doi.org/10.3390/ijms25168661 - 8 Aug 2024
Viewed by 256
Abstract
Many years ago, asbestos fibers were banned and replaced by synthetic vitreous fibers because of their carcinogenicity. However, the toxicity of the latter fibers is still under debate, especially when it concerns the early fiber interactions with biological cell membranes. Here, we aimed [...] Read more.
Many years ago, asbestos fibers were banned and replaced by synthetic vitreous fibers because of their carcinogenicity. However, the toxicity of the latter fibers is still under debate, especially when it concerns the early fiber interactions with biological cell membranes. Here, we aimed to investigate the effects of a synthetic vitreous fiber named FAV173 on the Xenopus laevis oocyte membrane, the cell model we have already used to characterize the effect of crocidolite asbestos fiber exposure. Using an electrophysiological approach, we found that, similarly to crocidolite asbestos, FAV173 was able to stimulate a chloride outward current evoked by step membrane depolarizations, that was blocked by the potent and specific TMEM16A channel antagonist Ani9. Exposure to FAV173 fibers also altered the oocyte cell membrane microvilli morphology similarly to crocidolite fibers, most likely as a consequence of the TMEM16A protein interaction with actin. However, FAV173 only partially mimicked the crocidolite fibers effects, even at higher fiber suspension concentrations. As expected, the crocidolite fibers’ effect was more similar to that induced by the co-treatment with (Fe3+ + H2O2), since the iron content of asbestos fibers is known to trigger reactive oxygen species (ROS) production. Taken together, our findings suggest that FAV173 may be less harmful that crocidolite but not ineffective in altering cell membrane properties. Full article
(This article belongs to the Section Molecular Biophysics)
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Figure 1

Figure 1
<p>(<b>a</b>) Example of SEM images of Croc and FAV173 fibers. (<b>b</b>) Vitelline membrane of non-treated (Ctrl), Croc-treated, and ground FAV173-treated oocytes. Note, in (<b>b</b>), a Croc fiber partially inserted into the pore of the vitelline membrane. Croc = 15 μg/mL, FAV173 = 200 μg/mL.</p>
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<p>Dose–response effect of FAV173 fiber exposure (from 15 to 400 μg/mL) on resting potential (RP) in (<b>a</b>) and membrane resistance (R<sub>m</sub>) in (<b>b</b>). In (<b>a</b>,<b>b</b>), the green bars show the effect of 15 μg/mL of Croc for comparison. The effect of FAV173 and Croc is expressed as % of decrease with respect to untreated cells (Ctrl) from the same donor. * <span class="html-italic">p</span> &lt; 0.05, *** <span class="html-italic">p</span> &lt; 0.001 fibers vs. Ctrl (unpaired <span class="html-italic">t</span>-test). In (<b>c</b>), the time course effect of Croc and FAV treatments on RP (<span class="html-italic">n</span> ≥ 3 donors). <sup>§§§</sup> <span class="html-italic">p</span> &lt; 0.001 FAV173 vs. Croc, <sup>##</sup> <span class="html-italic">p</span> &lt; 0.01 Croc (15–20) vs. Croc (5–10), (unpaired <span class="html-italic">t</span>-test). In (<b>d</b>), the effect on RP was irreversible only at higher fiber concentrations in Croc-treated cells (120 min, Croc: 45 μg/mL; FAV173: 600 μg/mL). *** <span class="html-italic">p</span> &lt; 0.001 Croc vs. Ctrl (one-way ANOVA with Tukey’s post hoc).</p>
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<p>In (<b>a</b>), examples of current traces recorded by stepping the membrane potential from −80 to +40 mV (10 mV steps, 3 s, V<sub>h</sub> = −40 mV) in non-treated (Ctrl, black), Croc-treated (green), and FAV173-treated (red) cells. (<b>b</b>) I–V relationships from Ctrl, Croc-treated, and FAV173-treated cells (same batch). Note the outward rectification in treated cells. (<b>c</b>) Percentage increase in the evoked current amplitude measured at −80 mV and +40 mV and normalized to their respective Ctrl (of the same donor). *** <span class="html-italic">p</span> &lt; 0.001, Fiber-treatments vs. Ctrl; <sup>§§</sup> <span class="html-italic">p</span> &lt; 0.001, Croc vs. FAV173 (unpaired <span class="html-italic">t</span>-test). Croc: 15 μg/mL; FAV173: 200 μg/mL.</p>
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<p>(<b>a</b>, <b>left</b>) Examples of recording traces from Ctrl cells in normal bathing solution, in presence of [Ca<sup>2+</sup>]<sub>e</sub> = 11 mM (Ca11) and Ca11 + Ani9 (1 μM). (<b>a</b>, <b>right</b>) I–V relationships in Ctrl (normal bathing solution), Ca11, and Ca11 + Ani9 (1 μM) conditions. Note that, in Ca11, the currents at negative potentials increased with respect to those recorded in normal bathing solution, and the evident blocking effect of Ani9. (<b>b</b>, <b>left</b>) Evoked currents from FAV173-treated (200 μg/mL) cells in presence of Ca11 and Ca11 + Ani9 (1 μM). (<b>b</b>, <b>right</b>) The I–V relationships revealed a significant increase in the evoked currents at positive and negative potentials in presence of Ca11 and a partial blocking effect induced by Ani9. Ctrl: <span class="html-italic">n</span> = 5; FAV173: <span class="html-italic">n</span> = 7, same donor. * <span class="html-italic">p</span> &lt; 0.05, *** <span class="html-italic">p</span> &lt; 0.001, Fibers vs. Ctrl (unpaired <span class="html-italic">t</span>-test); <sup>§</sup> <span class="html-italic">p</span> &lt; 0.05, <sup>§§</sup> <span class="html-italic">p</span> &lt; 0.01, <sup>§§§</sup> <span class="html-italic">p</span> &lt; 0.001, Ca11 vs. Ca11 + Ani9 (paired <span class="html-italic">t</span>-test).</p>
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<p>Example of SEM images of microvilli in (<b>a</b>) Ctrl oocyte, and oocytes in Ca11 bath condition in the absence and in the presence of FAV173 (200 μg/mL). In the inset of Ctrl, the vitelline membrane (VM) above the microvilli (MV) is shown. The FAV173 effect on the diameter (<b>b</b>) and density (<b>c</b>) of the microvilli (<b>c</b>), *** <span class="html-italic">p</span> &lt; 0.001 vs. Ca11 (unpaired <span class="html-italic">t</span>-test). In (<b>d</b>) microvilli of Croc and (Fe<sup>3+</sup> + H<sub>2</sub>O<sub>2</sub>)-treated oocytes. Comparison of microvilli diameter (<b>e</b>) and density (<b>f</b>) values measured under the 3 test conditions (* <span class="html-italic">p</span> &lt; 0.05, *** <span class="html-italic">p</span> &lt; 0.001 vs. Ctrl, <sup>§</sup> <span class="html-italic">p</span> &lt; 0.05, <sup>§§§</sup> <span class="html-italic">p</span> &lt; 0.001 (Fe<sup>3+</sup> + H<sub>2</sub>O<sub>2</sub>) vs. Croc, One-Way ANOVA with Tukey’s post hoc). Cells were treated for 60 min. (values are in the text). Scale bar 1 μm.</p>
Full article ">Figure 6
<p>(<b>a</b>) Comparison of RP values in oocytes in the presence of CyTD alone (<span class="html-italic">n</span> = 5), or with FAV173 (<span class="html-italic">n</span> = 13) and Ani9 (<span class="html-italic">n</span> = 13), Croc (<span class="html-italic">n</span> = 12) and Ani9 (<span class="html-italic">n</span> = 15), (Fe<sup>3+</sup> + H<sub>2</sub>O<sub>2</sub>) (<span class="html-italic">n</span> = 12), and Ani9 (<span class="html-italic">n</span> = 14). * <span class="html-italic">p</span> &lt; 0.05, ** <span class="html-italic">p</span> &lt; 0.01, *** <span class="html-italic">p</span> &lt; 0.001 vs. CyTD, <sup>§§§</sup> <span class="html-italic">p</span> &lt; 0.001 CyTD + Croc vs. CyTD + Croc + Ani9 (ANOVA with Tukey’s post hoc). (<b>b</b>) Examples of SEM images of the plasmalemma from CyTD, CyTD + Croc, and (Fe<sup>3+</sup> + H<sub>2</sub>O<sub>2</sub>) + CyTD-treated oocytes. In both cases, damage on the plasmalemma are visible (red asterisks). In (<b>c</b>), the presence of Ani9 fully recovered the membrane damage in the Croc-treated cells, while it is still visible in (Fe<sup>3+</sup> + H<sub>2</sub>O<sub>2</sub>)-treated cells (white asterisk). Scale bar: 1 μm.</p>
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19 pages, 5893 KiB  
Article
Dead-Time Free Modulation Scheme for IM Drive System Fed by Voltage Source Inverter
by Qiwei Xu, Liangwu Yi, Xuehan Long, Lingyan Luo and Yiru Miao
Energies 2024, 17(15), 3845; https://doi.org/10.3390/en17153845 - 5 Aug 2024
Viewed by 304
Abstract
During the modulation process of the VSI motor drive system, the nonlinear errors caused by the dead-time and conduction voltage drop will increase the phase current harmonic distortion and the torque ripple. To solve this problem, a novel dead-time free modulation scheme is [...] Read more.
During the modulation process of the VSI motor drive system, the nonlinear errors caused by the dead-time and conduction voltage drop will increase the phase current harmonic distortion and the torque ripple. To solve this problem, a novel dead-time free modulation scheme is proposed in this paper. In the non-zero crossing region of the phase current, the switching tube, whose body diode can provide a continuation path, is set as off-state, the driving signal is only implemented on another switching tube with the same bridge arm, and the errors caused by the conduction voltage drop and switching delay are compensated to the pulse duration. At the same time, to suppress the zero current clamp effect that exists near the zero crossing point of the phase current, another modulation scheme for the phase current crossing zero in advance is proposed, which avoids the complicated determination and calculation of the current polarity near the zero crossing point of the current. Both of the above modulation schemes eliminate the dead-time, and the switching principle is presented. In addition, to suppress the impact of the current ripple and high-frequency noise on the accuracy of the phase current detection, a second-order resonance digital filter without phase shift is introduced. Finally, compared to two deadtime compensation methods, the effectiveness and superiority of the proposed dead-time free modulation scheme are verified by the experimental results. Full article
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Figure 1

Figure 1
<p>Topology of the induction motor drive system fed by VSI.</p>
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<p>Single phase leg configuration of VSI.</p>
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<p>Dead-time effects on the output voltage.</p>
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<p>Diagram of the zero current clamping effect. (<b>a</b>) Driving signal of upper leg. (<b>b</b>) Driving signal of lower leg. (<b>c</b>) voltage <span class="html-italic">v</span><sub>ao</sub> between point a and point o. (<b>d</b>) Ideal current and real current.</p>
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<p>Modulation diagram of dead-time elimination.</p>
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<p>Diagram of the phase current crossing zero in advance.</p>
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<p>Diagram of modulation switching within a fundamental period. (<b>a</b>) Description of current changes. (<b>b</b>) State transition diagram.</p>
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<p>Bode plot of filter transfer function.</p>
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<p>The waveforms of the phase current before and after digital filter.</p>
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<p>The flow chart of the modulation selection based on the digital filter.</p>
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<p>Experimental platform.</p>
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<p>Diagram of the closed-loop control system.</p>
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<p>Experimental waveforms under compensation of the pulse duration when IM operates at 500 r/min and 4 N·m. (<b>a</b>) Phase current. (<b>b</b>) Harmonic analysis results. (<b>c</b>) Power spectral density. (<b>d</b>) Torque.</p>
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<p>Experimental waveforms under inverter nonlinearity feedforward compensation when IM operates at 500 r/min and 4 N·m. (<b>a</b>) Phase current. (<b>b</b>) Harmonic analysis results. (<b>c</b>) Power spectral density. (<b>d</b>) Torque.</p>
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<p>Experimental waveforms under proposed dead-time free modulation when IM operates at 500 r/min and 4 N·m. (<b>a</b>) Phase current. (<b>b</b>) Harmonic analysis results. (<b>c</b>) Power spectral density. (<b>d</b>) Torque.</p>
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<p>Experimental waveforms under compensation of the pulse duration when IM operates at 3000 r/min and 0 N·m. (<b>a</b>) Phase current. (<b>b</b>) Harmonic analysis results. (<b>c</b>) Power spectral density. (<b>d</b>) Torque.</p>
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<p>Experimental waveforms under inverter nonlinearity feedforward compensation when IM operates at 3000 r/min and 0 N·m. (<b>a</b>) Phase current. (<b>b</b>) Harmonic analysis results. (<b>c</b>) Power spectral density. (<b>d</b>) Torque.</p>
Full article ">Figure 18
<p>Experimental waveforms under proposed dead-time free modulation when IM operates at 3000 r/min and 0 N·m. (<b>a</b>) Phase current. (<b>b</b>) Harmonic analysis results. (<b>c</b>) Power spectral density. (<b>d</b>) Torque.</p>
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<p>Experimental waveforms under compensation of the pulse duration when IM operates at 1500 r/min and 4 N·m. (<b>a</b>) Phase current. (<b>b</b>) Harmonic analysis results. (<b>c</b>) Power spectral density. (<b>d</b>) Torque.</p>
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<p>Experimental waveforms under inverter nonlinearity feedforward compensation when IM operates at 1500 r/min and 4 N·m. (<b>a</b>) Phase current. (<b>b</b>) Harmonic analysis results. (<b>c</b>) Power spectral density. (<b>d</b>) Torque.</p>
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<p>Experimental waveforms under proposed dead-time free modulation when IM operates at 1500 r/min and 4 N·m. (<b>a</b>) Phase current. (<b>b</b>) Harmonic analysis results. (<b>c</b>) Power spectral density. (<b>d</b>) Torque.</p>
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<p>The diagram of the inverter nonlinearity feedforward compensation.</p>
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36 pages, 28072 KiB  
Article
Four-Wire Three-Level NPC Shunt Active Power Filter Using Model Predictive Control Based on the Grid-Tied PV System for Power Quality Enhancement
by Zoubida Amrani, Abdelkader Beladel, Abdellah Kouzou, Jose Rodriguez and Mohamed Abdelrahem
Energies 2024, 17(15), 3822; https://doi.org/10.3390/en17153822 - 2 Aug 2024
Viewed by 440
Abstract
The primary objective of this paper focuses on developing a control approach to improve the operational performance of a three-level neutral point clamped (3LNPC) shunt active power filter (SAPF) within a grid-tied PV system configuration. Indeed, this developed control approach, based on the [...] Read more.
The primary objective of this paper focuses on developing a control approach to improve the operational performance of a three-level neutral point clamped (3LNPC) shunt active power filter (SAPF) within a grid-tied PV system configuration. Indeed, this developed control approach, based on the used 3LNPC-SAPF topology, aims to ensure the seamless integration of a photovoltaic system into the three-phase four-wire grid while effectively mitigating grid harmonics, grid current unbalance, ensuring grid unit power factor by compensating the load reactive power, and allowing power sharing with the grid in case of an excess of generated power from the PV system, leading to overall high power quality at the grid side. This developed approach is based initially on the application of the four-wire instantaneous p-q theory for the identification of the reference currents that have to be injected by the 3LNPC-SAPF in the grid point of common coupling (PCC). Whereas, the 3LNPC is controlled based on using the finite control set model predictive control (FCS-MPC), which can be accomplished by determining the convenient set of switch states leading to the voltage vector, which is the most suitable to ensure the minimization of the selected cost function. Furthermore, the used topology requires a constant DC-link voltage and balanced split-capacitor voltages at the input side of the 3LNPN. Hence, the cost function is adjusted by the addition of another term with a selected weighting factor related to these voltages to ensure their precise control following the required reference values. However, due to the random changes in solar irradiance and, furthermore, to ensure efficient operation of the proposed topology, the PV system is connected to the 3LNPN-SAPF via a DC/DC boost converter to ensure the stability of the 3LNPN input voltage within the reference value, which is achieved in this paper based on the use of the maximum power point tracking (MPPT) technique. For the validation of the proposed control technique and the functionality of the used topology, a set of simulations has been presented and investigated in this paper following different irradiance profile scenarios such as a constant irradiance profile and a variables irradiance profile where the main aim is to prove the effectiveness and flexibility of the proposed approach under variable irradiance conditions. The obtained results based on the simulations carried out in this study demonstrate that the proposed control approach with the used topology under different loads such as linear, non-linear, and unbalanced can effectively reduce the harmonics, eliminating the unbalance in the currents and compensating for the reactive component contained in the grid side. The obtained results prove also that the proposed control ensures a consistent flow of power based on the sharing principle between the grid and the PV system as well as enabling the efficient satisfaction of the load demand. It can be said that the proposal presented in this paper has been proven to have many dominant features such as the ability to accurately estimate the power sharing between the grid and the PV system for ensuring the harmonics elimination, the reactive power compensation, and the elimination of the neutral current based on the zero-sequence component compensation, even under variable irradiance conditions. This feature makes the used topology and the developed control a valuable tool for power quality improvement and grid stability enhancement with low cost and under clean energy. Full article
(This article belongs to the Section A2: Solar Energy and Photovoltaic Systems)
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<p>Proposed configuration of the grid connected to two-stage photovoltaic systems using an active power filter (APF) with a control strategy that is based on a three-level NPC inverter.</p>
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<p>Single diode model of the PV module.</p>
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<p>PV array at 25 °C and specified irradiances (250, 500 and 1000 w/m<sup>2</sup>), (<b>a</b>) the out put current versu the out put voltage, (<b>b</b>) the output power versus the output voltage.</p>
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<p>Boost topology.</p>
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<p>Flowchart of the P and O algorithm.</p>
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<p>Three-level NPC multilevel converter power circuit.</p>
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<p>An analogous circuit consisting of an APF that is linked in parallel.</p>
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<p>The illustration of reference current calculation.</p>
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<p>Diagram and fundamental concepts of model predictive control.</p>
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<p>The flowchart demonstrates the implementation of the suggested FSC-MPC.</p>
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<p>Irradiance profiles. (<b>a</b>) profile of constant irradiance, (<b>b</b>) profile of variable irradiance.</p>
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<p>Three-phase load currents.</p>
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<p>Load current and voltage.</p>
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<p>Grid current and voltage.</p>
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<p>Active and reactive power of load, APF, and grid.</p>
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<p>Neutral current.</p>
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<p>DC-link voltage.</p>
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<p>Grid voltage and current.</p>
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<p>Three-phase grid currents.</p>
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<p>Neutral current.</p>
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<p>Active and reactive power of load, APF, and grid.</p>
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<p>DC-link voltage.</p>
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<p>Three-phase load currents.</p>
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<p>Three-phase grid currents.</p>
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<p>Load voltage and current.</p>
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<p>Grid voltage and current.</p>
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<p>Active and reactive power of load, APF, and grid.</p>
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<p>DC link voltage.</p>
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<p>Three-phase grid currents.</p>
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<p>Grid voltage and current.</p>
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<p>Active and reactive power of load, APF, and grid.</p>
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<p>DC link voltage.</p>
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<p>Three-phase load currents.</p>
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<p>Three-phase grid currents.</p>
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<p>Active and reactive power of load, APF, and grid.</p>
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<p>Grid voltage and current.</p>
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<p>Neutral current.</p>
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<p>DC link voltage.</p>
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<p>Three-phase grid currents.</p>
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<p>Grid voltage and current.</p>
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<p>Active and reactive power of load, APF, and grid.</p>
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<p>DC link voltage.</p>
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<p>Neutral current.</p>
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<p>Power sharing impacts on quality of grid current.</p>
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14 pages, 3760 KiB  
Article
The Biallelic Inheritance of Two Novel SCN1A Variants Results in Developmental and Epileptic Encephalopathy Responsive to Levetiracetam
by Giorgia Dinoi, Elena Conte, Orazio Palumbo, Mario Benvenuto, Maria Antonietta Coppola, Pietro Palumbo, Patrizia Lastella, Brigida Boccanegra, Ester Di Muro, Marco Castori, Massimo Carella, Vittorio Sciruicchio, Marina de Tommaso, Antonella Liantonio, Annamaria De Luca, Angela La Neve and Paola Imbrici
Biomedicines 2024, 12(8), 1698; https://doi.org/10.3390/biomedicines12081698 - 31 Jul 2024
Viewed by 324
Abstract
Loss-, gain-of-function and mixed variants in SCN1A (Nav1.1 voltage-gated sodium channel) have been associated with a spectrum of neurologic disorders with different severity and drug-responsiveness. Most SCN1A variants are heterozygous changes occurring de novo or dominantly inherited; recessive inheritance has been reported in [...] Read more.
Loss-, gain-of-function and mixed variants in SCN1A (Nav1.1 voltage-gated sodium channel) have been associated with a spectrum of neurologic disorders with different severity and drug-responsiveness. Most SCN1A variants are heterozygous changes occurring de novo or dominantly inherited; recessive inheritance has been reported in a few cases. Here, we report a family in which the biallelic inheritance of two novel SCN1A variants, N935Y and H1393Q, occurs in two siblings presenting with drug-responsive developmental and epileptic encephalopathy and born to heterozygous asymptomatic parents. To assess the genotype–phenotype correlation and support the treatment choice, HEK 293 cells were transfected with different combinations of the SCN1A WT and mutant cDNAs, and the resulting sodium currents were recorded through whole-cell patch-clamp. Functional studies showed that the N935Y and H1393Q channels and their combinations with the WT (WT + N935Y and WT + H1393Q) had current densities and biophysical properties comparable with those of their respective control conditions. This explains the asymptomatic condition of the probands’ parents. The co-expression of the N935Y + H1393Q channels, mimicking the recessive inheritance of the two variants in siblings, showed ~20% reduced current amplitude compared with WT and with parental channels. This mild loss of Nav1.1 function may contribute in part to the disease pathogenesis, although other mechanisms may be involved. Full article
(This article belongs to the Special Issue Epilepsy: From Mechanisms to Therapeutic Approaches)
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<p>(<b>A</b>) Pedigree of the family displaying the compound heterozygous variant. Filled and unfilled circles/squares represent affected and unaffected individuals, respectively. (<b>B</b>) Electropherograms of DNA sequencing for the probands (II.1, II.2) and their parents (I.1, I.2). The variants c.2803A&gt;T, p.(Asn935Tyr), inherited from the father, and c.4179T&gt;A, p.(His1393Gln), inherited from the mother, identified here, are indicated by red and blue arrows, respectively.</p>
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<p>(<b>A</b>) Schematic representation of the Nav1.1 channel, showing the amino acidic substitutions involved in biallelic inheritance (<a href="#biomedicines-12-01698-t001" class="html-table">Table 1</a>). Red dots represent the identified mutations N935Y and H1393Q; and (<b>B</b>) Amino acid alignment of Nav1 channels.</p>
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<p>(<b>A</b>) Representative current traces evoked by 20 ms depolarizing steps from a holding potential of −150 mV to +70 mV from Nav1.1 WT (7 μg), N935Y (7 μg) and H1393Q (7 μg) channels expressed in HEK 293 cells. The voltage protocol is indicated in the upper panel in (<b>A</b>); (<b>B</b>) Current–voltage relationship for Nav1.1 WT, N935Y and H1393Q channels (n = 10–12). The inset shows current density measured at −10 mV for the three channel types; (<b>C</b>) Voltage-dependent activation curves for Nav1.1 WT, N935Y and H1393Q channels were obtained by plotting the normalized conductance as a function of the membrane potentials and fitting data points with a Boltzmann function (n = 9–10 cells). The inset shows V<sub>1/2</sub> values for the four channel types; (<b>D</b>) Steady-state fast inactivation curves for Nav1.1 WT, N935Y and H1393Q channels were obtained by plotting the normalized peak tail currents measured at −20 mV as a function of the prepulse potentials and fitting data points with a Boltzmann function (n = 9–14 cells). The inset shows V<sub>1/2</sub> values for the four channel types; and (<b>E</b>) Bar graphs showing the time constants of the fast inactivation measured at −10 mV for the indicated channels, calculated by fitting current decay with a double exponential function (n = 14 cells).</p>
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<p>(<b>A</b>) Representative current traces evoked by 20 ms depolarizing steps from a holding potential of −150 mV to +70 mV from Nav1.1 WT + Nav1.1 WT (14 μg), Nav1.1 WT + N935Y (14 μg), Nav1.1 WT + H1393Q (14 μg) and N935Y + H1393Q (14 μg) channels expressed in HEK 293 cells. The voltage protocol is indicated in the upper panel in (<b>A</b>); (<b>B</b>) Current–voltage relationship for Nav1.1 WT + Nav1.1 WT, Nav1.1 WT + N935Y, Nav1.1 WT + H1393Q and N935Y + H1393Q channels (n = 14–22). The inset shows current density measured at −10 mV for the four channel types; (<b>C</b>) Voltage-dependent activation curves for Nav1.1 WT + Nav1.1 WT, Nav1.1 WT + N935Y, Nav1.1 WT + H1393Q and N935Y + H1393Q channels were obtained by plotting the normalized conductance as a function of the membrane potentials and fitting data points with a Boltzmann function (n = 13–29 cells). The inset shows V<sub>1/2</sub> values for the four channel types; (<b>D</b>) Steady-state inactivation curves for Nav1.1 WT + Nav1.1 WT, Nav1.1 WT + N935Y, Nav1.1 WT + H1393Q and N935Y + H1393Q channels were obtained by plotting the normalized peak tail currents measured at −20 mV as a function of the prepulse potentials and fitting data points with a Boltzmann function (n = 11–27 cells). The inset shows V<sub>1/2</sub> values for the four channel types; and (<b>E</b>) Bar graphs showing the time constants of the fast inactivation measured at −10 mV for the indicated channels, calculated by fitting current decay with a double exponential function (n = 12–25 cells).</p>
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18 pages, 5475 KiB  
Article
Interleaved Modified SEPIC Converters with Soft Switching and High Power Factor for LED Lighting Appliance
by Hung-Liang Cheng, Chun-An Cheng, Chien-Hsuan Chang, En-Chih Chang, Lain-Chyr Hwang and Yi-Chan Hung
Appl. Sci. 2024, 14(15), 6656; https://doi.org/10.3390/app14156656 - 30 Jul 2024
Viewed by 387
Abstract
A novel ac/dc LED driver with power factor correction and soft-switching functions is proposed. The circuit topology mainly consists of two modified single-ended primary inductance converters (SEPIC) with interleaved operation. The first half stage of SEPIC operates like a boost converter and the [...] Read more.
A novel ac/dc LED driver with power factor correction and soft-switching functions is proposed. The circuit topology mainly consists of two modified single-ended primary inductance converters (SEPIC) with interleaved operation. The first half stage of SEPIC operates like a boost converter and the second half stage operates like a buck–boost converter. Each boost converter is designed to operate in discontinuous current mode (DCM) to function as a power factor corrector (PFC). The two buck–boost converters that share a commonly coupled inductor are designed to operate at near boundary conduction mode (BCM). Without using any active clamping circuit, auxiliary switch or snubber circuit, the active switches can achieve zero-voltage switching on, and all diodes achieve zero-current switching off. First, operation modes in steady state are analyzed, and the mathematical equations for design component parameters are derived. Finally, a prototype circuit of 180 W rated power was built and tested. Experimental results show satisfactory performance of the proposed circuit. Full article
(This article belongs to the Section Optics and Lasers)
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<p>Proposed LED driver.</p>
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<p>Gate-to-source voltages of <span class="html-italic">S</span><sub>1</sub> and <span class="html-italic">S</span><sub>2</sub>.</p>
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<p>Operation modes (<b>a</b>) Mode 1; (<b>b</b>) Mode 2; (<b>c</b>) Mode 3; (<b>d</b>) Mode 4; (<b>e</b>) Mode 5; (<b>f</b>) Mode 6; (<b>g</b>) Mode 7; (<b>h</b>) Mode 8; (<b>i</b>) Mode 9; and (<b>j</b>) Mode 10.</p>
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<p>Operation modes (<b>a</b>) Mode 1; (<b>b</b>) Mode 2; (<b>c</b>) Mode 3; (<b>d</b>) Mode 4; (<b>e</b>) Mode 5; (<b>f</b>) Mode 6; (<b>g</b>) Mode 7; (<b>h</b>) Mode 8; (<b>i</b>) Mode 9; and (<b>j</b>) Mode 10.</p>
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<p>Schematic waveforms.</p>
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<p>Gate−to−source voltages. (<span class="html-italic">v<sub>GS</sub></span><sub>1</sub>: 5 V/div, <span class="html-italic">v<sub>GS</sub></span><sub>2</sub>: 5 V/div, time: 5 µs/div).</p>
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<p>Inductor currents of the PFC converters. (<b>a</b>) <span class="html-italic">i<sub>p</sub></span><sub>1</sub> and <span class="html-italic">i<sub>p</sub></span><sub>2</sub> for several input voltage cycles. (<span class="html-italic">i<sub>p</sub></span><sub>1</sub>, <span class="html-italic">i<sub>p</sub></span><sub>2</sub>: 2 A/div, time: 5 ms/div), (<b>b</b>) expanded waveforms of <span class="html-italic">i<sub>p</sub></span><sub>1</sub> and <span class="html-italic">i<sub>p</sub></span><sub>2</sub> when the input voltage is near the peak value. (<span class="html-italic">i<sub>p</sub></span><sub>1</sub>, <span class="html-italic">i<sub>p</sub></span><sub>2</sub>: 2 A/div, time: 5 µs/div).</p>
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<p>(<b>a</b>) Waveforms of the input voltage and current. (<span class="html-italic">v<sub>in</sub></span>: 50 V/div, <span class="html-italic">i<sub>in</sub></span>: 2 A/div, time: 5 ms/div), and (<b>b</b>) comparison between measured input current harmonics and IEC standard [<a href="#B6-applsci-14-06656" class="html-bibr">6</a>].</p>
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<p>Waveforms of leakage current of <span class="html-italic">T</span><sub>1</sub>. (<span class="html-italic">i<sub>Ll</sub></span><sub>1</sub>, <span class="html-italic">i<sub>Ll</sub></span><sub>2</sub>: 0.5 A/div, time: 5 μs/div).</p>
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<p>Waveforms of <span class="html-italic">S</span><sub>1</sub> and <span class="html-italic">S</span><sub>2</sub>. (<b>a</b>) <span class="html-italic">v<sub>GS</sub></span><sub>1</sub>, <span class="html-italic">v<sub>DS</sub></span><sub>1</sub> and <span class="html-italic">i<sub>S</sub></span><sub>1</sub>. (<span class="html-italic">v<sub>GS</sub></span><sub>1</sub>: 10 V/div, <span class="html-italic">v<sub>DS</sub></span><sub>1</sub>: 200 V/div, <span class="html-italic">i<sub>S</sub></span><sub>1</sub>: 1 A/div, time: 5 μs/div). (<b>b</b>) <span class="html-italic">v<sub>GS</sub></span><sub>2</sub>, <span class="html-italic">v<sub>DS</sub></span><sub>2</sub> and <span class="html-italic">i<sub>S</sub></span><sub>2</sub>. (<span class="html-italic">v<sub>GS</sub></span><sub>2</sub>: 10 V/div, <span class="html-italic">v<sub>DS</sub></span><sub>2</sub>: 200 V/div, <span class="html-italic">i<sub>S</sub></span><sub>2</sub>: 1 A/div, time: 5 μs/div).</p>
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<p>Waveforms of LED voltage and LED current. (<span class="html-italic">V<sub>LED</sub></span>: 100 V/div, <span class="html-italic">I<sub>LED</sub></span>: 1 A/div, time: 5 ms/div).</p>
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<p>Photo of the proposed LED driver test stand.</p>
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16 pages, 944 KiB  
Article
A Novel Repeat PI Decoupling Control Strategy with Linear Active Disturbance Rejection for a Three-Level Neutral-Point-Clamped Active Power Filter with an LCL Filter
by Yifei Gao, Liancheng Zhu, Xiaoyang Wang, Xiaoguo Lv and Hongshi Wei
Electronics 2024, 13(15), 2973; https://doi.org/10.3390/electronics13152973 - 28 Jul 2024
Viewed by 356
Abstract
The three-level neutral-point-clamped (NPC) active power filter (APF) is suitable for harmonic compensation in high voltage and large capacity applications. And, the harmonic compensation effect of APF depends on its dynamic performance and control. This paper propose a repeat proportional integral (PI) decoupling [...] Read more.
The three-level neutral-point-clamped (NPC) active power filter (APF) is suitable for harmonic compensation in high voltage and large capacity applications. And, the harmonic compensation effect of APF depends on its dynamic performance and control. This paper propose a repeat proportional integral (PI) decoupling control strategy with linear active disturbance rejection (LADRC) to address the issues of detection in complex harmonic current and power supply current distortion when the nonlinear load varies. To simplify the design of LADRC, this paper adopts inverter current feedback control. Firstly, repeat control is introduced to optimize the traditional PI controller, which improves the compensation accuracy while ensuring the dynamic response capability of the control system. Then, to address the serious coupling of the system model in the d-q coordinate system, a reduced order linear active disturbance rejection (LADRC) control is introduced. The PI and linear extended state observer (LESO) control method is adopted in the outer voltage loop to maintain stable DC voltage and improve the ability to suppress voltage overshoot during grid connection. The effectiveness of this control method has been verified through MATLAB/Simlink. The results show that, compared with the repeat PI method, the control method based on repeat PI–LADRC can achieve better decoupling control, improve robustness and anti-interference ability, enhance the performance of the original system, and can significantly improve the harmonic suppression capability of the APF. Full article
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<p>Topology of the neutral-point-clamped three-level active power filter.</p>
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<p>The principle structure diagram of the LCL filter.</p>
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<p>Block diagram of repeat control system structure.</p>
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<p>Bode diagram of the controlled object.</p>
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<p>Nyquist curve of <math display="inline"><semantics> <mrow> <msup> <mi>z</mi> <mn>5</mn> </msup> <msub> <mi>G</mi> <mrow> <mi>L</mi> <mn>1</mn> <mi>f</mi> </mrow> </msub> <mrow> <mo>(</mo> <mi>z</mi> <mo>)</mo> </mrow> <mi>S</mi> <mrow> <mo>(</mo> <mi>z</mi> <mo>)</mo> </mrow> </mrow> </semantics></math>.</p>
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<p>The structure diagram of repeat PI.</p>
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<p>The structure diagram of LADRC.</p>
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<p>The structure diagram of repeat PI–LADRC.</p>
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<p>The structure diagram of PI and LESO.</p>
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<p>Tracking current diagram during steady-state. (<b>a</b>) Repeat PI–LADRC decoupling control. (<b>b</b>) Repeat PI control.</p>
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<p>DC-side voltage during steady-state. (<b>a</b>) When the load current is 84 A. (<b>b</b>) When the load current is 129 A.</p>
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<p>Simulation of APF startup using repeat PI control. (<b>a</b>) Filter tracking current. (<b>b</b>) Phase a grid current.</p>
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<p>Simulation of APF startup using repeat PI–LADRC decoupling control. (<b>a</b>) Filter tracking current. (<b>b</b>) Phase a grid current.</p>
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<p>Simulation of harmonic load switching for repeat PI control. (<b>a</b>) Filter tracking current. (<b>b</b>) Phase a grid current.</p>
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<p>Simulation of harmonic load switching for repeat PI–LADRC decoupling control. (<b>a</b>) Filter tracking current. (<b>b</b>) Phase a grid current.</p>
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<p>DC-side voltage. (<b>a</b>) Simulation at the time of APF startup. (<b>b</b>) Simulation at the time of harmonic load switching.</p>
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18 pages, 6366 KiB  
Article
In Silico Screening Identification of Fatty Acids and Fatty Acid Derivatives with Antiseizure Activity: In Vitro and In Vivo Validation
by Emilia Mercedes Barrionuevo, Estefanía Peralta, Agustín Manzur De Nardi, Juliana Monat, Maximiliano José Fallico, Manuel Augusto Llanos, Luciana Gavernet, Emilio Román Mustafá, Pedro Martin and Alan Talevi
Pharmaceutics 2024, 16(8), 996; https://doi.org/10.3390/pharmaceutics16080996 - 27 Jul 2024
Viewed by 495
Abstract
High fat diets have been used as complementary treatments for seizure disorders for more than a century. Moreover, many fatty acids and derivatives, including the broad-spectrum antiseizure medication valproic acid, have been explored and used as pharmacological agents to treat epilepsy. In this [...] Read more.
High fat diets have been used as complementary treatments for seizure disorders for more than a century. Moreover, many fatty acids and derivatives, including the broad-spectrum antiseizure medication valproic acid, have been explored and used as pharmacological agents to treat epilepsy. In this work, we have explored the anticonvulsant potential of a large library of fatty acids and fatty acid derivatives, the LIPID MAPS Structure Database, using structure-based virtual screening to assess their ability to block the voltage-gated sodium channel 1.2 (NaV1.2), a validated target for antiseizure medications. Four of the resulting in silico hits were submitted for experimental confirmation using in vitro patch clamp experiments, and their protective role was evaluated in an acute mice seizure model, the Maximal Electroshock seizure model. These four compounds were found to protect mice against seizures. Two of them exhibited blocking effects on NaV1.2, CaV2.2, and CaV3.1. Full article
(This article belongs to the Special Issue Computer-Aided Development: Recent Advances and Expectations)
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<p>Docking poses vs. hNaV1.2 of the selected in silico hits submitted to in vivo and in vitro assays. The top scoring pose for each ligand is shown. Residues constituting the DEKA ring are represented in pink, while residues F1118 (FS6) and Y1125 from the Ab site are depicted in yellow. Compounds were selected based on the ligand’s efficiency, visual inspection of the poses, and favorable drug-like properties: 5-hexenoic acid (orange), 2-aminooctanoic acid (green), 9-phenylnonanoic acid (blue), and 9-hydroxydecanoic acid (violet). (<b>A</b>) Front view of hNaV1.2 along with the top scoring docking poses for the selected compounds. (<b>B</b>) 5-hexenoic acid’s highest score docking pose showing a 2.7 Å hydrogen bond with SER815 and a 3.7 Å minimal distance to FS6. (<b>C</b>) 2-aminooctanoic acid’s highest score docking pose showing a 1.9 Å hydrogen bond with SER815 and a 3.6 Å minimal distance to FS6. (<b>D</b>) 9-phenylnonanoic acid’s highest score docking pose showing a 3.6 Å pi-interaction with PHE535, a 3.0 Å hydrogen bond with TYR1125, and a 4.9 Å minimal distance to FS6. (<b>E</b>) 9-hydroxydecanoic acid’s highest score docking pose showing a 2.7 Å hydrogen bond with SER815, a 2.2 Å hydrogen bond to SER1117, and a 3.6 Å minimal distance to FS6.</p>
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<p>NaV1.1 current inhibition. Representative traces (<b>top</b>) and time courses (<b>middle</b>) of normalized NaV1.1 current (INaV1.1) from HEK293 cells with stable expression of NaV1.1 channels in control condition and 5-hexanoic acid (100 µM) application (n = 5, panel (<b>A</b>)); 2-aminooctanoic acid (100 µM) application (n = 7, panel (<b>B</b>)); 9-hydroxydecanoic acid (100 µM) application (n = 8, panel (<b>C</b>)); or 9-phenylnonanoic acid (100 µM) application (n = 7, panel (<b>D</b>)). Bars (<b>bottom</b>) represent normalized INaV1.1 in control condition and with each compound. Statistical significance was evaluated by one-sample <span class="html-italic">t</span>-test against 1.</p>
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<p>NaV1.2 current inhibition. Representative traces (<b>top</b>) and time courses (<b>middle</b>) of normalized NaV1.2 current (INaV1.2) from HEK293 cells with stable expression of NaV1.2 channels in control condition and 5-hexanoic acid (100 µM) application (n = 7, panel (<b>A</b>)); 2-aminooctanoic acid (100 µM) application (n = 7, panel (<b>B</b>)); 9-hydroxydecanoic acid (100 µM) application (n = 7, panel (<b>C</b>)); or 9-phenylnonanoicacid (100 µM) application (n = 10, panel (<b>D</b>)). Bars (<b>bottom</b>) represent normalized INaV1.2 in control condition and with each compound. Statistical significance was evaluated by one-sample <span class="html-italic">t</span>-test against 1.</p>
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<p>Mechanism of NaV channel inhibition by fatty acids. (<b>A</b>). Typical traces of human NaV1.1 (<b>left</b>) and NaV1.2 (<b>right</b>) currents evoked by the steady-state inactivation protocol under control conditions and after the application of 100 μM 9-hydroxydecanoic acid. (<b>B</b>). Mean h-curves obtained for control conditions and after stable effect of 100 µM 5-hexanoic acid (5-HEX, orange, NaV1.1: n = 5, NaV1.2: n = 5), 2-aminooctanoic acid (2-AO, green, NaV1.1: n = 7, NaV1.2: n = 5), 9-hydroxydecanoic acid (9-HiD, violet, NaV1.1: n = 8, NaV1.2: n = 7), and 9-phenylnonanoic acid (9-PhN, blue, NaV1.1: n = 6, NaV1.2: n = 10). (<b>C</b>). Mean change in half-maximal voltage inactivation (ΔV1/2) values obtained from the h-curves calculated for each fatty acid. # indicates statistically significant differences between ΔV1/2 values and 0 mV (one-sample <span class="html-italic">t</span>-test, <span class="html-italic">p</span> &lt; 0.05); * indicates statistically significant differences between isoforms in the obtained ΔV1/2 values (unpaired <span class="html-italic">t</span>-test, <span class="html-italic">p</span> &lt; 0.05). The slope parameter remained unchanged in all the treatments. (<b>D</b>). Mean voltage-independent inhibition, observed as a reduction in the Na+ current elicited after a pre-conditioning pulse of −130 mV (Imax) obtained after fatty acid treatment and normalized to control current value. # indicates statistically significant differences between Imax values and 1 (one-sample <span class="html-italic">t</span>-test, <span class="html-italic">p</span> &lt; 0.05); * indicates statistically significant differences between isoforms in the obtained Imax values (unpaired <span class="html-italic">t</span>-test, <span class="html-italic">p</span> &lt; 0.05).</p>
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<p>CaV3.1 current inhibition. Representative traces (<b>top</b>) and time courses (<b>middle</b>) of normalized CaV3.1 current (ICaV3.1) from HEK293T cells transfected with CaV3.1 in control condition and 5-hexanoic acid (100 µM) application (n = 4, panel (<b>A</b>)); 2-aminooctanoic acid (100 µM) application (n = 5, panel (<b>B</b>)); 9-hydroxydecanoic acid (100 µM) application (n = 5, panel (<b>C</b>)); or 9-phenylnonanoic acid (100 µM) application (n = 5, panel (<b>D</b>)). Bars (<b>bottom</b>) represent normalized ICaV3.1 in control condition and with each compound. Statistical significance was evaluated by one-sample <span class="html-italic">t</span>-test against 1.</p>
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<p>CaV2.2 current inhibition. Representative traces (<b>top</b>) and time courses (<b>middle</b>) of normalized CaV2.2 current (ICaV2.2) from HEK293T cells transfected with CaV2.2 in control condition and 5-hexanoic acid (100 µM) application (n = 3, panel (<b>A</b>)); 2-aminooctanoic acid (100 µM) application (n = 4, panel (<b>B</b>)); 9-hydroxydecanoic acid (100 µM) application (n = 3, panel (<b>C</b>)); or 9-phenylnonanoic acid (100 µM) application (n = 4, panel (<b>D</b>)). Bars (<b>bottom</b>) represent normalized ICaV2.2 in control condition and with each compound. Statistical significance was evaluated by one-sample <span class="html-italic">t</span>-test against 1.</p>
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<p>Molecular dynamics simulations. The distance between the carbonyl carbon of carboxylic acid and the oxygen of the protein side chain was monitored along 25 ns of simulation (n = 3). (<b>A</b>) 9-phenylnonanoic acid interaction with Tyr1125; (<b>B</b>) 9-hydroxydecanoic acid interaction with Ser815.</p>
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17 pages, 9179 KiB  
Article
Hybrid ANPC Grid-Tied Inverter Design with Passivity-Based Sliding Mode Control Strategy
by Yifei Zhang, Kang Li and Li Zhang
Energies 2024, 17(15), 3655; https://doi.org/10.3390/en17153655 - 25 Jul 2024
Viewed by 375
Abstract
Voltage source inverters are extensively used in the grid connection of renewable energy-sourced generators, and multilevel converters, in particular, have attracted a great deal of attention in recent years. This paper investigates the application of a novel passivity-based sliding mode (PSM) control scheme [...] Read more.
Voltage source inverters are extensively used in the grid connection of renewable energy-sourced generators, and multilevel converters, in particular, have attracted a great deal of attention in recent years. This paper investigates the application of a novel passivity-based sliding mode (PSM) control scheme on three-level grid-tie active Neutral-Point-Clamped (ANPC) inverters that yield fast and stable responses to grid impedance variations. Simulation studies confirm that this control scheme can produce high tracking performance and is also robust against grid load variations. Furthermore, to enhance ANPC efficiency, the loss distribution of switching devices controlled by the proposed strategy is evaluated. An optimal scheme is finally proposed for allocating silicon and Wide-Band-Gap switching devices, resulting in a hybrid ANPC inverter capable of achieving a desirable trade-off between the power losses and the device cost. Full article
(This article belongs to the Special Issue Energy, Electrical and Power Engineering 2024)
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<p>A three-phase hybrid ANPC grid-tied inverter circuit.</p>
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<p>PS-PWM scheme. Blue and red triangle waves are two carrier waves with a 180° phase difference; Black sine wave is reference wave.</p>
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<p>States of PS-PWM control: (<b>a</b>) positive cycle; (<b>b</b>) two ZVS for positive state; (<b>c</b>) negative cycle; (<b>d</b>) two ZVS for negative state.</p>
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<p>Switching states of PS-SWM control. (<b>a</b>) positive cycle; (<b>b</b>) negative cycle. Blue and red triangle waves are two carrier waves with a 180° phase difference; Black sine wave is reference wave. The red square wave represents the PWM waveform in the positive cycle while the blue one represents it in the negative cycle.</p>
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<p>Block diagram of the grid-tied inverter equivalent circuit model.</p>
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<p>Block diagram of passive controller.</p>
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<p>Block diagram of PSM controller.</p>
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<p>Diagram of the system.</p>
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<p>Passive control with load mutation. The red, blue, and black lines are three phase current waves.</p>
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<p>PSM with load mutation.</p>
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<p>SMC with load mutation.</p>
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<p>Passive control with different reference currents.</p>
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<p>PSM with different reference currents.</p>
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<p>SMC with different reference currents.</p>
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<p>Loss distribution of switches.</p>
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<p>Hybrid structure.</p>
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<p>Si/SiC hybrid structure.</p>
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<p>Si/GaN hybrid structure.</p>
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16 pages, 4890 KiB  
Article
An Active Clamp Dual-Inductor Isolated Current Source to Current Source Converter with Wide Output Voltage Range
by Tiesheng Yan, Wenyuan Chen, Yu Zhou, Dong Lin, Jun Tian and Guohua Zhou
Electronics 2024, 13(15), 2925; https://doi.org/10.3390/electronics13152925 - 24 Jul 2024
Viewed by 355
Abstract
Human observation of the ocean has gradually evolved from the sea surface to systematic monitoring and sampling through seafloor observation networks, and constant current power supply has become the main power supply method for seafloor observation networks due to its high reliability. There [...] Read more.
Human observation of the ocean has gradually evolved from the sea surface to systematic monitoring and sampling through seafloor observation networks, and constant current power supply has become the main power supply method for seafloor observation networks due to its high reliability. There are some studies on current source to voltage source converters, but there are few studies on current source to current source (CS/CS) converters, which affects the expansion of power supply networks for seafloor observation networks. In this paper, by employing input current sharing and output voltage doubling circuits, an active clamp dual-inductor isolated CS/CS converter which uses a single-stage conversion circuit to realize constant current source conversion with a wide output voltage range is proposed. Active clamp technology at the primary side of the proposed circuit is employed to recover energy stored in leakage inductance, suppress voltage spikes of the primary side switches, and achieve zero-voltage switching of the primary side switches. The secondary side’s output voltage doubling circuit resonates with transformer leakage inductance to achieve zero-current switching of the secondary side diodes, which can reduce losses and enhance efficiency. The operating principles of the proposed circuit are analyzed in detail, and the characteristic and parameter design analysis, including current conversion ratio, transformer turn ratio, power inductors, and resonant capacitors and inductor, are presented. Finally, the experimental results based on a 100 W experimental prototype validate the feasibility of the proposed converter. Full article
(This article belongs to the Topic Power Electronics Converters)
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<p>Block diagram of a submarine observation network.</p>
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<p>Main circuit and control circuit block diagram of the proposed active clamped dual-inductor isolated CS/CS converter. (<b>a</b>) Main circuit topology; (<b>b</b>) Control circuit.</p>
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<p>Operation modes during the first half of the switching cycle. (<b>a</b>) Mode A; (<b>b</b>) Mode B; (<b>c</b>) Mode C; (<b>d</b>) Mode D; (<b>e</b>) Mode E.</p>
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<p>Operation modes during the first half of the switching cycle. (<b>a</b>) Mode A; (<b>b</b>) Mode B; (<b>c</b>) Mode C; (<b>d</b>) Mode D; (<b>e</b>) Mode E.</p>
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<p>Main waveforms of the proposed topology.</p>
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<p>Experimental prototype. (<b>a</b>) Top side of main circuit board; (<b>b</b>) Bottom side of main circuit board; (<b>c</b>) Control circuit.</p>
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<p>Experimental platform.</p>
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<p>Test waveforms of input current <span class="html-italic">I<sub>in</sub></span>, input voltage <span class="html-italic">V<sub>in</sub></span>, output current <span class="html-italic">I<sub>o</sub></span>, and output voltage <span class="html-italic">V<sub>o</sub></span> with different output loads. (<b>a</b>) 100% load; (<b>b</b>) 80% load; (<b>c</b>) 50% load; (<b>d</b>) 10% load.</p>
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<p>Test waveforms of primary voltage <span class="html-italic">v<sub>TP</sub></span> of transformer, primary current <span class="html-italic">i</span><sub>P</sub> of transformer, secondary current <span class="html-italic">i<sub>S</sub></span> of transformer, and clamp capacitor voltage <span class="html-italic">v<sub>Cc</sub></span> with different loads. (<b>a</b>) 100% load; (<b>b</b>) 10% load.</p>
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<p>Test waveforms of inductor currents <span class="html-italic">i<sub>L</sub></span><sub>1</sub> and <span class="html-italic">i<sub>L</sub></span><sub>2</sub> and driver signals of <span class="html-italic">S</span><sub>1</sub> and <span class="html-italic">S</span><sub>2</sub> with different output loads. (<b>a</b>) 100% load; (<b>b</b>) 10% load.</p>
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<p>Experimental results of efficiency with different output voltage loads.</p>
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16 pages, 2861 KiB  
Article
Crosstalk among WEE1 Kinase, AKT, and GSK3 in Nav1.2 Channelosome Regulation
by Aditya K. Singh, Jully Singh, Nana A. Goode and Fernanda Laezza
Int. J. Mol. Sci. 2024, 25(15), 8069; https://doi.org/10.3390/ijms25158069 - 24 Jul 2024
Viewed by 439
Abstract
The signaling complex around voltage-gated sodium (Nav) channels includes accessory proteins and kinases crucial for regulating neuronal firing. Previous studies showed that one such kinase, WEE1—critical to the cell cycle—selectively modulates Nav1.2 channel activity through the accessory protein fibroblast growth factor 14 (FGF14). [...] Read more.
The signaling complex around voltage-gated sodium (Nav) channels includes accessory proteins and kinases crucial for regulating neuronal firing. Previous studies showed that one such kinase, WEE1—critical to the cell cycle—selectively modulates Nav1.2 channel activity through the accessory protein fibroblast growth factor 14 (FGF14). Here, we tested whether WEE1 exhibits crosstalk with the AKT/GSK3 kinase pathway for coordinated regulation of FGF14/Nav1.2 channel complex assembly and function. Using the in-cell split luciferase complementation assay (LCA), we found that the WEE1 inhibitor II and GSK3 inhibitor XIII reduce the FGF14/Nav1.2 complex formation, while the AKT inhibitor triciribine increases it. However, combining WEE1 inhibitor II with either one of the other two inhibitors abolished its effect on the FGF14/Nav1.2 complex formation. Whole-cell voltage-clamp recordings of sodium currents (INa) in HEK293 cells co-expressing Nav1.2 channels and FGF14-GFP showed that WEE1 inhibitor II significantly suppresses peak INa density, both alone and in the presence of triciribine or GSK3 inhibitor XIII, despite the latter inhibitor’s opposite effects on INa. Additionally, WEE1 inhibitor II slowed the tau of fast inactivation and caused depolarizing shifts in the voltage dependence of activation and inactivation. These phenotypes either prevailed or were additive when combined with triciribine but were outcompeted when both WEE1 inhibitor II and GSK3 inhibitor XIII were present. Concerted regulation by WEE1 inhibitor II, triciribine, and GSK3 inhibitor XIII was also observed in long-term inactivation and use dependency of Nav1.2 currents. Overall, these findings suggest a complex role for WEE1 kinase—in concert with the AKT/GSK3 pathway—in regulating the Nav1.2 channelosome. Full article
(This article belongs to the Special Issue Protein Kinases in Neurological Disorders)
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<p>Evaluation of the effects of kinase inhibitors on the FGF14/Nav1.2 complex assembly using the in-cell split luciferase complementation assay (LCA). (<b>A</b>) Representative bar graph (top) and dose-response graph (bottom) of % luminescence reflecting the FGF14/Nav1.2 complex assembly in response to WEE1 inhibitor II (1–150 µM), (<b>B</b>) the AKT inhibitor (0.5–100 µM), and (<b>C</b>) GSK3 inhibitor XIII (1–150 µM). (<b>D</b>,<b>E</b>) are representative bar graphs (top) and dose responses (bottom) of % luminescence reflecting the FGF14/Nav1.2 complex assembly in response to WEE1 inhibitor II (15 µM) in combination with the indicated inhibitors. Percentage of luminescence (normalized to per plate control wells treated with 0.5% DMSO; <span class="html-italic">n</span> = 8 wells per plate) is plotted as a function of log concentration in the dose–response graphs at the bottom. Data are represented ± SEM. <span class="html-italic">Half maximal inhibitory concentration</span> (IC<sub>50</sub>) and half maximal effective concentration (EC<sub>50</sub>) were calculated using a sigmoidal dose–response fitting.</p>
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<p>The interplay between WEE1 inhibitor II, triciribine, and GSK3 inhibitor XIII in regulating Nav1.2-mediated I<sub>Na</sub>. (<b>A</b>) Representative traces of I<sub>Na</sub> from HEK293-Nav1.2 cells expressing FGF14-GFP (HEK-Nav1.2/FGF14). Traces were recorded in response to depolarizing voltage steps in the presence of WEE1 inhibitor II (WEE1; 10 µM), triciribine (tri; 10 µM), GSK3 inhibitor XIII (30 µM), and/or DMSO (0.01%); the voltage-clamp stimulating protocol is depicted on the right. (<b>B</b>) Current-voltage (I-V) relationships derived from the experimental groups are described in Panel (<b>A</b>). (<b>C</b>) Bar graphs representing peak current densities and (<b>D</b>) the time constant (tau) of fast inactivation of Nav1.2 channels from the experimental groups are described in Panel (<b>A</b>). Data are presented as mean ± SEM. Statistical significance is indicated as follows: * <span class="html-italic">p</span> &lt; 0.05, ** <span class="html-italic">p</span> &lt; 0.001, *** <span class="html-italic">p</span> &lt; 0.0001, ns = nonsignificant, determined by one-way ANOVA followed by Tukey’s multiple comparisons test (<span class="html-italic">n</span> = 6–10). In this figure, GSK3 inhibitor XIII is referred to as XIII.</p>
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<p>Synergy and competition between WEE1 inhibitor II, triciribine, and GSK3 inhibitor XIII in regulating Na<sub>v</sub>1.2 channel voltage dependence of activation and steady-state inactivation. (<b>A</b>) Normalized conductance plotted as a function of the voltage in HEK-Nav1.2/FGF14 cells treated with 0.1% DMSO or respective kinase inhibitors as shown with color-coded labels. The data were fitted with the Boltzmann function. (<b>B</b>) Bar graph summary of V<sub>1/2</sub> of activation. (<b>C</b>) Voltage dependence of steady-state inactivation. (<b>D</b>) Bar graph summary of V<sub>1/2</sub> of inactivation. Data are presented as mean ± SEM. Statistical significance is indicated as * <span class="html-italic">p</span> &lt; 0.05, ** <span class="html-italic">p</span> &lt; 0.001, *** <span class="html-italic">p</span> &lt; 0.0001, ns = nonsignificant, determined by one-way ANOVA followed by Tukey’s multiple comparisons test (<span class="html-italic">n</span> = 6–10). In this figure, GSK3 inhibitor XIII is referred to as XIII.</p>
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<p>Crosstalk among WEE1 inhibitor, triciribine, and GSK3 inhibitor XIII on modulation of Na<sub>v</sub>1.2 channel long-term inactivation and cumulative inactivation properties. (<b>A</b>) Representative traces of <span class="html-italic">I</span><sub>Na</sub> elicited by HEK-Nav1.2/FGF14 cells from the indicated experimental groups in response to the depicted voltage-clamp protocol to induce long-term inactivation. (<b>B</b>) Long-term inactivation of Nav1.2 measured as channel availability versus depolarization. (<b>C</b>) Comparison of the relative <span class="html-italic">I</span><sub>Na</sub> amplitude at the 1st pulse to the 4th pulse for the indicated experimental groups. (<b>D</b>) Representative traces of <span class="html-italic">I</span><sub>Na</sub> elicited by HEK-Nav1.2/FGF14 cells from the indicated experimental groups in response to the depicted voltage-clamp protocol to induce use-dependent cumulative inactivation. (<b>E</b>) Characterization of cumulative inactivation of Nav1.2 channels induced by use dependency for the experimental groups described in (<b>D</b>). (<b>F</b>) Comparison of the relative <span class="html-italic">I</span><sub>Na</sub> amplitude at the 1st pulse to the 20th pulse for the indicated experimental groups. Data are presented as mean ± SEM. Statistical significance is indicated as * <span class="html-italic">p</span> &lt; 0.05, ** <span class="html-italic">p</span> &lt; 0.001, *** <span class="html-italic">p</span> &lt; 0.0001, ns = nonsignificant, determined by one-way ANOVA followed by Tukey’s multiple comparisons test (<span class="html-italic">n</span> = 6–10). In this figure, GSK3 inhibitor XIII is referred to as XIII.</p>
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<p>Putative crosstalk between WEE1 kinase, AKT, and GSK3 in regulating the Nav1.2/FGF14 signalosome. WEE1 kinase and GSK3β have been shown to directly regulate the FGF14/Nav1.2 complex assembly and its functional activity via phosphorylation of FGF14Y158 (1) and FGF14S226 (2), respectively. Additionally, GSK3β directly phosphorylates the Nav1.2 C-terminal tail at T1966 (3). Phosphorylation of FGF14Y158 by WEE1 kinase may increase its assembly with Nav1.2. Similarly, phosphorylation of FGF14S226 or Nav1.2T1966 by GSK3 may enhance the assembly of the FGF14/Nav1.2 complex. Moreover, GSK3 has been shown to degrade WEE1 kinase via ubiquitination (4), leading to a reduction in WEE1 kinase levels. There are no reports of direct phosphorylation of FGF14 or Nav1.2 by AKT. Therefore, AKT may influence the FGF14/Nav1.2 complex assembly and its functional activity indirectly through the suppression of GSK3β via inhibitory phosphorylation (5) or through a synergistic effect with WEE1 kinase (6).</p>
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18 pages, 8559 KiB  
Article
Three-Coil Wireless Charging System Based on S-PS Topology
by Kai Yan, Ruirong Dang and Wenzhen Wang
Energies 2024, 17(15), 3606; https://doi.org/10.3390/en17153606 - 23 Jul 2024
Viewed by 321
Abstract
To protect the battery, radio energy transmission charging typically uses constant current (CC) charging before switching to constant voltage (CV) charging to enhance battery durability. This paper proposes adding an auxiliary clamp coil to the original circuit topology. The IPT battery charger designed [...] Read more.
To protect the battery, radio energy transmission charging typically uses constant current (CC) charging before switching to constant voltage (CV) charging to enhance battery durability. This paper proposes adding an auxiliary clamp coil to the original circuit topology. The IPT battery charger designed with the auxiliary clamp coil can achieve both constant current (CC) and constant voltage (CV) outputs. The mutual inductance between the auxiliary clamp coil and the primary side coil greatly influences the output performance of the entire IPT system, so the auxiliary clamp coil should not be too large. To solve this problem, an S-S-PS circuit with secondary compensation topology in the secondary coil is proposed. This circuit topology reduces the size of the auxiliary clamp coil, allowing it to be placed in an optimal position. When the constant voltage output critical position is reached, the IPT system can still automatically, continuously, and smoothly switch between CC and CV modes. Consequently, this approach avoids increased cost consumption associated with detecting CC-CV switching thresholds, adding wireless transmission communication modules, real-time control of the power transmitter, and active protection of the circuit during constant current charging. Finally, a 48 V/2.5 A prototype was built to verify that the IPT system has CC-CV conversion functionality. Full article
(This article belongs to the Section F: Electrical Engineering)
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<p>Three-coil (S-S-S) IPT system.</p>
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<p>Equivalent circuit for three coils.</p>
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<p>Two-port equivalent circuit of secondary edge compensation network.</p>
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<p>S-S-PS three-coil IPT system.</p>
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<p>S-S-PS three-coil equivalent circuit.</p>
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<p>Conduction state diagram of auxiliary clamp loop rectifier bridge. (<b>a</b>) No conduction, (<b>b</b>) extreme conduction, (<b>c</b>) conduction angle &lt; <math display="inline"><semantics> <mrow> <mstyle scriptlevel="0" displaystyle="true"> <mfrac> <mi>π</mi> <mn>2</mn> </mfrac> </mstyle> </mrow> </semantics></math>, (<b>d</b>) fully conductive.</p>
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<p>Current and voltage transmission characteristics of S-S-PS three-coil charging system.</p>
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<p>Lithium battery charging principle prototype platform.</p>
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<p>Structure of three-coil coupling mechanism.</p>
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<p>Load <math display="inline"><semantics> <mrow> <msub> <mi>R</mi> <mi>L</mi> </msub> <mo>=</mo> <mn>10</mn> <mtext> </mtext> <mo>Ω</mo> </mrow> </semantics></math> output state waveform. (<b>a</b>) <span class="html-italic">I</span><sub>P</sub>, <span class="html-italic">V</span><sub>P</sub> primary input voltage and current, <span class="html-italic">I</span><sub>R</sub>, <span class="html-italic">V</span><sub>R</sub> secondary output current and voltage (<b>b</b>) <span class="html-italic">I</span><sub>A</sub>, <span class="html-italic">V</span><sub>A</sub> auxiliary coil current and voltage, <span class="html-italic">I</span><sub>0</sub> is the load current.</p>
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<p>Load <math display="inline"><semantics> <mrow> <msub> <mi>R</mi> <mi>L</mi> </msub> <mo>=</mo> <mn>20</mn> <mtext> </mtext> <mo>Ω</mo> </mrow> </semantics></math> output state waveform. (<b>a</b>) <span class="html-italic">I</span><sub>P</sub>, <span class="html-italic">V</span><sub>P</sub> primary input voltage and current, <span class="html-italic">I</span><sub>R</sub>, <span class="html-italic">V</span><sub>R</sub> secondary output current and voltage (<b>b</b>) <span class="html-italic">I</span><sub>A</sub>, <span class="html-italic">V</span><sub>A</sub> auxiliary coil current and voltage, <span class="html-italic">I</span><sub>0</sub> is the load current.</p>
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<p>Load <math display="inline"><semantics> <mrow> <msub> <mi>R</mi> <mi>L</mi> </msub> <mo>=</mo> <mn>100</mn> <mtext> </mtext> <mo>Ω</mo> </mrow> </semantics></math> output state waveform. (<b>a</b>) <span class="html-italic">I</span><sub>P</sub>, <span class="html-italic">V</span><sub>P</sub> primary input voltage and current, <span class="html-italic">I</span><sub>R</sub>, <span class="html-italic">V</span><sub>R</sub> secondary output current and voltage (<b>b</b>) <span class="html-italic">I</span><sub>A</sub>, <span class="html-italic">V</span><sub>A</sub> auxiliary coil current and voltage, <span class="html-italic">I</span><sub>0</sub> is the load current.</p>
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<p>Dynamic curve of voltage and current at the output terminal.</p>
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<p>Dynamic graph of IPT system output efficiency.</p>
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19 pages, 5673 KiB  
Article
A Live Detecting System for Strain Clamps of Transmission Lines Based on Dual UAVs’ Cooperation
by Zhiwei Jia, Yongkang Ouyang, Chao Feng, Shaosheng Fan, Zheng Liu and Chenhao Sun
Drones 2024, 8(7), 333; https://doi.org/10.3390/drones8070333 - 19 Jul 2024
Viewed by 491
Abstract
Strain clamps are critical components in high-voltage overhead transmission lines, and detection of their defects becomes an important part of regular inspection of transmission lines. A dual UAV (unmanned aerial vehicle) system was proposed to detect strain clamps in multiple split-phase conductors. The [...] Read more.
Strain clamps are critical components in high-voltage overhead transmission lines, and detection of their defects becomes an important part of regular inspection of transmission lines. A dual UAV (unmanned aerial vehicle) system was proposed to detect strain clamps in multiple split-phase conductors. The main UAV was equipped with a digital radiography (DR) imaging device, a mechanical arm, and an edge intelligence module with visual sensors. The slave UAV was equipped with a digital imaging board and visual sensors. A workflow was proposed for this dual UAV system. Target detection and distance detection of the strain clamps, as well as detection of the defects of strain clamps in DR images, are the main procedures of this workflow. To satisfy the demands of UAV-borne and real-time deployment, the improved YOLOv8-TR algorithm was proposed for the detection of strain clamps (the mAP@50 was 60.9%), and the KD-ResRPA algorithm is used for detecting defects in DR images (the average AUCROC of the three datasets was 82.7%). Field experiments validated the suitability of our dual UAV-based system for charged detection of strain clamps in double split-phase conductors, demonstrating its potential for practical application in live detecting systems. Full article
(This article belongs to the Special Issue Embodied Artificial Intelligence Systems for UAVs)
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<p>DR imaging technique to detect the double split-phase wire diagram.</p>
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<p>Integrated dual UAV system.</p>
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<p>Process of the dual UAV system’s operation.</p>
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<p>Structure of YOLOv8-TR.</p>
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<p>The C2f-G-Ghost module and the G-Ghost bottleneck module.</p>
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<p>The transformation of the world coordinate system and the pixels’ coordinate system.</p>
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<p>The KD-ResRPA unsupervised model of detecting anomalies based on an attention enhancement mechanism.</p>
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<p>Residual assistance module.</p>
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<p>Pyramid attention module.</p>
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<p>The sample dataset of Self-data-RGB.</p>
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<p>Comparison of the results of practical application. (<b>a</b>) The original algorithm’s detection of the images. (<b>b</b>) The improved algorithm’s detection of the images.</p>
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<p>Anomalous images of strain clamps: (<b>a</b>) typical shot anomaly; (<b>b</b>) typical defect anomaly (the red box marks the defect’s location).</p>
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<p>Test results of different models on the self-made strain clamp dataset. All models were trained and tested on Datasets A, B, and C, and evaluated using the average AUCROC (%) of the three tests.</p>
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<p>Physical picture of the main UAV and slave UAV. (<b>a</b>) main UAV; (<b>b</b>) slave UAV.</p>
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<p>Live field detection. (<b>a</b>) Relative position of the twin drones during detection. (<b>b</b>) Returned X-ray images of strain clamps and the test results.</p>
Full article ">
19 pages, 6990 KiB  
Article
A Reconfigurable Phase-Shifted Full-Bridge DC–DC Converter with Wide Range Output Voltage
by Jhon Brajhan Benites Quispe, Marcello Mezaroba, Alessandro Luiz Batschauer and Jean Marcos de Souza Ribeiro
Energies 2024, 17(14), 3483; https://doi.org/10.3390/en17143483 - 15 Jul 2024
Viewed by 512
Abstract
This paper analyzes, designs and implements a reconfigurable phase-shifted full-bridge (PSFB) converter. It adopts the topology of the traditional PSFB converter and incorporates clamping circuits to solve some fundamental problems of conventional topology. In addition, auxiliary switches are employed for output reconfiguration, which [...] Read more.
This paper analyzes, designs and implements a reconfigurable phase-shifted full-bridge (PSFB) converter. It adopts the topology of the traditional PSFB converter and incorporates clamping circuits to solve some fundamental problems of conventional topology. In addition, auxiliary switches are employed for output reconfiguration, which allows expanding the output voltage range without compromising the system efficiency. Single pole double throw (SPDT) mechanical switches are used to realize series and parallel connections. In this paper, the characterization of the PSFB converter with clamping circuit and its design considerations are discussed. A 10 kW prototype with a power density of 0.485 W/cm3, 900 V input voltage and 400/800 V nominal output voltage was manufactured. The experimental results validated the analysis and confirmed the high conversion efficiency for a wide load range; an efficiency of 96.69% was obtained for the full load condition. Full article
Show Figures

Figure 1

Figure 1
<p>Circuit diagram of the proposed reconfigurable PSFB converter adapted from [<a href="#B28-energies-17-03483" class="html-bibr">28</a>].</p>
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<p>Equivalent circuit of the proposed reconfigurable PSFB converter.</p>
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<p>Key waveforms of the equivalent circuit in <a href="#energies-17-03483-f002" class="html-fig">Figure 2</a>.</p>
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<p>Operation modes of the equivalent circuit in <a href="#energies-17-03483-f002" class="html-fig">Figure 2</a>.</p>
Full article ">Figure 5
<p>Relationship surfaces according to <span class="html-italic">D</span> and <math display="inline"><semantics> <msub> <mi>I</mi> <mrow> <mi>l</mi> <mi>o</mi> <mi>n</mi> <mo>(</mo> <mi>e</mi> <mi>f</mi> <mo>)</mo> </mrow> </msub> </semantics></math> adapted from [<a href="#B28-energies-17-03483" class="html-bibr">28</a>].</p>
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<p>Control block diagram.</p>
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<p>Prototype of the proposed reconfigurable PSFB converter.</p>
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<p>Reconfigurable PSFB converter prototype test scheme.</p>
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<p>Parallel connection case: experimental waveforms in the leading leg under full load condition. (<b>a</b>) Waveforms of the drain-source voltage <math display="inline"><semantics> <msub> <mi>v</mi> <mrow> <mi>d</mi> <mi>s</mi> <mo>,</mo> <mi>q</mi> <mn>2</mn> </mrow> </msub> </semantics></math> and gate-source voltage <math display="inline"><semantics> <msub> <mi>v</mi> <mrow> <mi>g</mi> <mi>s</mi> <mo>,</mo> <mi>q</mi> <mn>2</mn> </mrow> </msub> </semantics></math> of switch <math display="inline"><semantics> <msub> <mi>Q</mi> <mn>2</mn> </msub> </semantics></math>, primary current <math display="inline"><semantics> <msub> <mi>i</mi> <mrow> <mi>p</mi> <mo>,</mo> <mn>1</mn> </mrow> </msub> </semantics></math>, and output current <math display="inline"><semantics> <msub> <mi>i</mi> <mi>o</mi> </msub> </semantics></math>. (<b>b</b>) ZVS waveforms.</p>
Full article ">Figure 10
<p>Parallel connection case: Experimental waveforms in the lagging leg under full load condition. (<b>a</b>) Waveforms of the drain-source voltage <math display="inline"><semantics> <msub> <mi>v</mi> <mrow> <mi>d</mi> <mi>s</mi> <mo>,</mo> <mi>q</mi> <mn>3</mn> </mrow> </msub> </semantics></math> and gate-source voltage <math display="inline"><semantics> <msub> <mi>v</mi> <mrow> <mi>g</mi> <mi>s</mi> <mo>,</mo> <mi>q</mi> <mn>3</mn> </mrow> </msub> </semantics></math> of switch <math display="inline"><semantics> <msub> <mi>Q</mi> <mn>3</mn> </msub> </semantics></math>, primary current <math display="inline"><semantics> <msub> <mi>i</mi> <mrow> <mi>p</mi> <mo>,</mo> <mn>1</mn> </mrow> </msub> </semantics></math>, and output current <math display="inline"><semantics> <msub> <mi>i</mi> <mi>o</mi> </msub> </semantics></math>. (<b>b</b>) ZVS waveforms.</p>
Full article ">Figure 11
<p>Parallel connection case: Experimental waveforms in the lagging leg under half load condition. (<b>a</b>) Waveforms of the drain-source voltage <math display="inline"><semantics> <msub> <mi>v</mi> <mrow> <mi>d</mi> <mi>s</mi> <mo>,</mo> <mi>q</mi> <mn>3</mn> </mrow> </msub> </semantics></math> and gate-source voltage <math display="inline"><semantics> <msub> <mi>v</mi> <mrow> <mi>g</mi> <mi>s</mi> <mo>,</mo> <mi>q</mi> <mn>3</mn> </mrow> </msub> </semantics></math> of switch <math display="inline"><semantics> <msub> <mi>Q</mi> <mn>3</mn> </msub> </semantics></math>, primary current <math display="inline"><semantics> <msub> <mi>i</mi> <mrow> <mi>p</mi> <mo>,</mo> <mn>1</mn> </mrow> </msub> </semantics></math>, and output current <math display="inline"><semantics> <msub> <mi>i</mi> <mi>o</mi> </msub> </semantics></math>. (<b>b</b>) LVS waveforms.</p>
Full article ">Figure 12
<p>Series connection case: Experimental waveforms in the leading leg under full load condition. (<b>a</b>) Waveforms of the drain-source voltage <math display="inline"><semantics> <msub> <mi>v</mi> <mrow> <mi>d</mi> <mi>s</mi> <mo>,</mo> <mi>q</mi> <mn>2</mn> </mrow> </msub> </semantics></math> and gate-source voltage <math display="inline"><semantics> <msub> <mi>v</mi> <mrow> <mi>g</mi> <mi>s</mi> <mo>,</mo> <mi>q</mi> <mn>2</mn> </mrow> </msub> </semantics></math> of switch <math display="inline"><semantics> <msub> <mi>Q</mi> <mn>2</mn> </msub> </semantics></math>, primary current <math display="inline"><semantics> <msub> <mi>i</mi> <mrow> <mi>p</mi> <mo>,</mo> <mn>1</mn> </mrow> </msub> </semantics></math>, and output current <math display="inline"><semantics> <msub> <mi>i</mi> <mi>o</mi> </msub> </semantics></math>. (<b>b</b>) ZVS waveforms.</p>
Full article ">Figure 13
<p>Series connection case: Experimental waveforms in the lagging leg under full load condition. (<b>a</b>) Waveforms of the drain-source voltage <math display="inline"><semantics> <msub> <mi>v</mi> <mrow> <mi>d</mi> <mi>s</mi> <mo>,</mo> <mi>q</mi> <mn>3</mn> </mrow> </msub> </semantics></math> and gate-source voltage <math display="inline"><semantics> <msub> <mi>v</mi> <mrow> <mi>g</mi> <mi>s</mi> <mo>,</mo> <mi>q</mi> <mn>3</mn> </mrow> </msub> </semantics></math> of switch <math display="inline"><semantics> <msub> <mi>Q</mi> <mn>3</mn> </msub> </semantics></math>, primary current <math display="inline"><semantics> <msub> <mi>i</mi> <mrow> <mi>p</mi> <mo>,</mo> <mn>1</mn> </mrow> </msub> </semantics></math>, and output current <math display="inline"><semantics> <msub> <mi>i</mi> <mi>o</mi> </msub> </semantics></math>. (<b>b</b>) ZVS waveforms.</p>
Full article ">Figure 14
<p>Series connection case: Experimental waveforms in the lagging leg under half load condition. (<b>a</b>) Waveforms of the drain-source voltage <math display="inline"><semantics> <msub> <mi>v</mi> <mrow> <mi>d</mi> <mi>s</mi> <mo>,</mo> <mi>q</mi> <mn>3</mn> </mrow> </msub> </semantics></math> and gate-source voltage <math display="inline"><semantics> <msub> <mi>v</mi> <mrow> <mi>g</mi> <mi>s</mi> <mo>,</mo> <mi>q</mi> <mn>3</mn> </mrow> </msub> </semantics></math> of switch <math display="inline"><semantics> <msub> <mi>Q</mi> <mn>3</mn> </msub> </semantics></math>, primary current <math display="inline"><semantics> <msub> <mi>i</mi> <mrow> <mi>p</mi> <mo>,</mo> <mn>1</mn> </mrow> </msub> </semantics></math>, and output current <math display="inline"><semantics> <msub> <mi>i</mi> <mi>o</mi> </msub> </semantics></math>. (<b>b</b>) LVS waveforms.</p>
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<p>Parallel connection case: Experimental waveforms for a load transient. (<b>a</b>) Output current from 12.5 A to 25 A. (<b>b</b>) Output current from 25 A to 12.5 A.</p>
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<p>Series connection case: Experimental waveforms for a load transient. (<b>a</b>) Output current from 6.25 A to 12.5 A. (<b>b</b>) Output current from 12.5 A to 6.25 A.</p>
Full article ">Figure 17
<p>Measured efficiency of the prototype.</p>
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12 pages, 15242 KiB  
Technical Note
Inherently Decoupled Dc-Link Capacitor Voltage Control of Multilevel Neutral-Point-Clamped Converters
by Gabriel Garcia-Rojas, Sergio Busquets-Monge, Robert Griñó and José M. Campos-Salazar
Electronics 2024, 13(13), 2671; https://doi.org/10.3390/electronics13132671 - 7 Jul 2024
Viewed by 684
Abstract
This letter derives and discusses the superiority of a simple dc-link capacitor voltage control configuration for multilevel neutral-point-clamped converters with any number of levels. The control involves n − 2 control loops regulating the difference between the voltage of neighbor capacitors. These control [...] Read more.
This letter derives and discusses the superiority of a simple dc-link capacitor voltage control configuration for multilevel neutral-point-clamped converters with any number of levels. The control involves n − 2 control loops regulating the difference between the voltage of neighbor capacitors. These control loops are inherently decoupled, i.e., they are independent and the control action of one loop does not affect the others. This method is proven to be equivalent to previously published approaches, with the added advantages of increased simplicity and scalability to a higher number of levels, all while imposing a lower computational burden. The good performance of such control is confirmed through simulations and experiments. Full article
(This article belongs to the Special Issue Multi-level Power Converters Systems)
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Figure 1

Figure 1
<p>Functional schematic of an <span class="html-italic">n</span>-level NPC converter leg.</p>
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<p>Examples of four-level NPC leg topologies. (<b>a</b>) Transistor clamped. (<b>b</b>) Reduced transistor clamped or π-type. (<b>c</b>) Diode clamped. (<b>d</b>) Reduced diode clamped.</p>
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<p>Proposed optimum control configuration for <span class="html-italic">n</span> levels.</p>
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<p>Control configuration in [<a href="#B5-electronics-13-02671" class="html-bibr">5</a>] (four-level case).</p>
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<p>System diagram of a four-level, three-phase NPC grid inverter.</p>
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<p>Complete control block diagram of a four-level, three-phase grid inverter. (<b>a</b>) Decoupled structure following [<a href="#B5-electronics-13-02671" class="html-bibr">5</a>]. (<b>b</b>) Proposed simplified decoupled structure.</p>
Full article ">Figure 6 Cont.
<p>Complete control block diagram of a four-level, three-phase grid inverter. (<b>a</b>) Decoupled structure following [<a href="#B5-electronics-13-02671" class="html-bibr">5</a>]. (<b>b</b>) Proposed simplified decoupled structure.</p>
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<p>System diagram of the three-phase, four-level NPC dc–ac converter employed in the simulations and in the experimental verification.</p>
Full article ">Figure 8
<p>Simulation results under unbalanced initial capacitor voltages of a four-level, three-phase system. Conditions: <span class="html-italic">V</span><sub>dc</sub> = 150 V, <span class="html-italic">m</span> = 0.5, <span class="html-italic">C</span> = 155 µF, R = 10 Ω, L = 10 mH, switching frequency <span class="html-italic">f</span><sub>s</sub> = 5 kHz, and <span class="html-italic">G</span><sub>c</sub>(<span class="html-italic">s</span>) = 0.02/[1 + <span class="html-italic">s</span>/(1000π)]. (<b>a</b>) Control disabled. (<b>b</b>) Control in [<a href="#B5-electronics-13-02671" class="html-bibr">5</a>] without decoupling. (<b>c</b>) Proposed inherently decoupled control from <a href="#electronics-13-02671-f003" class="html-fig">Figure 3</a>, which is exactly equivalent to the control in [<a href="#B5-electronics-13-02671" class="html-bibr">5</a>] with decoupling.</p>
Full article ">Figure 9
<p>Simulation results under ramp variations of the <span class="html-italic">v</span><sup>*</sup><sub>C2</sub> and <span class="html-italic">v</span><sup>*</sup><sub>C3</sub> commands of a four-level, three-phase system. Conditions: <span class="html-italic">V</span><sub>dc</sub> = 150 V, <span class="html-italic">m</span> = 0.5, <span class="html-italic">C</span> = 155 µF, R = 10 Ω, L = 10 mH, switching frequency <span class="html-italic">f</span><sub>s</sub> = 5 kHz, and <span class="html-italic">G</span><sub>c</sub>(<span class="html-italic">s</span>) = 0.02/[1 + <span class="html-italic">s</span>/(1000π)]. (<b>a</b>) Capacitor voltage command values. (<b>b</b>) Control in [<a href="#B5-electronics-13-02671" class="html-bibr">5</a>] without decoupling. (<b>c</b>) Proposed inherently decoupled control from <a href="#electronics-13-02671-f003" class="html-fig">Figure 3</a>, which is exactly equivalent to the control in [<a href="#B5-electronics-13-02671" class="html-bibr">5</a>] with decoupling.</p>
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<p>Simulation results under ramp variations of the <span class="html-italic">v</span><sup>*</sup><sub>C1</sub> and <span class="html-italic">v</span><sup>*</sup><sub>C4</sub> commands of a five-level, five-phase system. Conditions: <span class="html-italic">V</span><sub>dc</sub> = 200 V, <span class="html-italic">m</span> = 0.5, <span class="html-italic">C</span> = 200 µF, R = 10 Ω, L = 10 mH, <span class="html-italic">f</span><sub>s</sub> = 5 kHz, <span class="html-italic">G</span><sub>c</sub>(<span class="html-italic">s</span>) = 0.02/[1 + <span class="html-italic">s</span>/(1000π)]. (<b>a</b>) Capacitor voltage command values. (<b>b</b>) Control in [<a href="#B5-electronics-13-02671" class="html-bibr">5</a>] without decoupling. (<b>c</b>) Proposed inherently decoupled control from <a href="#electronics-13-02671-f003" class="html-fig">Figure 3</a>, which is exactly equivalent to the control in [<a href="#B5-electronics-13-02671" class="html-bibr">5</a>] with decoupling.</p>
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<p>Simulation results under ramp variations of the <span class="html-italic">v</span><sup>*</sup><sub>C1</sub>, <span class="html-italic">v</span><sup>*</sup><sub>C2</sub>, <span class="html-italic">v</span><sup>*</sup><sub>C5</sub>, and <span class="html-italic">v</span><sup>*</sup><sub>C6</sub> commands of a seven-level, five-phase system. Conditions: <span class="html-italic">V</span><sub>dc</sub> = 300 V, <span class="html-italic">m</span> = 0.5, <span class="html-italic">C</span> = 270 µF, R = 10 Ω, L = 10 mH, <span class="html-italic">f</span><sub>s</sub> = 5 kHz, <span class="html-italic">G</span><sub>c</sub>(<span class="html-italic">s</span>) = 0.02/[1 + <span class="html-italic">s</span>/(1000π)]. (<b>a</b>) Capacitor voltage command values. (<b>b</b>) Control in [<a href="#B5-electronics-13-02671" class="html-bibr">5</a>] without decoupling. (<b>c</b>) Proposed inherently decoupled control from <a href="#electronics-13-02671-f003" class="html-fig">Figure 3</a>, which is exactly equivalent to the control in [<a href="#B5-electronics-13-02671" class="html-bibr">5</a>] with decoupling.</p>
Full article ">Figure 12
<p>Simulation results under ramp variations of the <span class="html-italic">v</span><sup>*</sup><sub>C2</sub> and <span class="html-italic">v</span><sup>*</sup><sub>C3</sub> commands of a four-level, three-phase system with unbalanced dc-link capacitor values. Conditions: <span class="html-italic">V</span><sub>dc</sub> = 150 V, <span class="html-italic">m</span> = 0.5, <span class="html-italic">C</span><sub>1</sub> = 155 µF, <span class="html-italic">C</span><sub>2</sub> = 186 µF, <span class="html-italic">C</span><sub>3</sub> = 124 µF, R = 10 Ω, L = 10 mH, switching frequency <span class="html-italic">f</span><sub>s</sub> = 5 kHz, and <span class="html-italic">G</span><sub>c</sub>(<span class="html-italic">s</span>) = 0.02/[1 + <span class="html-italic">s</span>/(1000π)]. (<b>a</b>) Capacitor voltage command values. (<b>b</b>) Control in [<a href="#B5-electronics-13-02671" class="html-bibr">5</a>] without decoupling. (<b>c</b>) Proposed inherently decoupled control from <a href="#electronics-13-02671-f003" class="html-fig">Figure 3</a>, which is exactly equivalent to the control in [<a href="#B5-electronics-13-02671" class="html-bibr">5</a>] with decoupling.</p>
Full article ">Figure 13
<p>Simulation results under unbalanced capacitor leakage currents of a four-level, three-phase system with a proportional compensator. Conditions: <span class="html-italic">V</span><sub>dc</sub> = 150 V, <span class="html-italic">m</span> = 0.5, <span class="html-italic">C</span> = 465 µF, R<sub>C1__leakage</sub> = 100 kΩ, R<sub>C2__leakage</sub> = 100 kΩ, R<sub>C3__leakage</sub> = 2 kΩ, R = 10 Ω, L = 10 mH, switching frequency <span class="html-italic">f</span><sub>s</sub> = 5 kHz, and <span class="html-italic">G</span><sub>c</sub>(<span class="html-italic">s</span>) = 0.02/[1 + <span class="html-italic">s</span>/(1000π)]. (<b>a</b>) Control disabled. (<b>b</b>) Control in [<a href="#B5-electronics-13-02671" class="html-bibr">5</a>] without decoupling. (<b>c</b>) Proposed inherently decoupled control from <a href="#electronics-13-02671-f003" class="html-fig">Figure 3</a>, which is exactly equivalent to the control in [<a href="#B5-electronics-13-02671" class="html-bibr">5</a>] with decoupling.</p>
Full article ">Figure 14
<p>Simulation results under unbalanced capacitor leakage currents of a four-level, three-phase system with a proportional–integral compensator. Conditions: <span class="html-italic">V</span><sub>dc</sub> = 150 V, <span class="html-italic">m</span> = 0.5, <span class="html-italic">C</span> = 465 µF, R<sub>C1__leakage</sub> = 100 kΩ, R<sub>C2__leakage</sub> = 100 kΩ, R<sub>C3__leakage</sub> = 2 kΩ, R = 10 Ω, L = 10 mH, switching frequency <span class="html-italic">f</span><sub>s</sub> = 5 kHz, and <span class="html-italic">G</span><sub>c</sub>(<span class="html-italic">s</span>) = [0.02 + 1/s]/[1 + <span class="html-italic">s</span>/(1000π)]. (<b>a</b>) Control disabled. (<b>b</b>) Control in [<a href="#B5-electronics-13-02671" class="html-bibr">5</a>] without decoupling. (<b>c</b>) Proposed inherently decoupled control from <a href="#electronics-13-02671-f003" class="html-fig">Figure 3</a>, which is exactly equivalent to the control in [<a href="#B5-electronics-13-02671" class="html-bibr">5</a>] with decoupling.</p>
Full article ">Figure 15
<p>Laboratory prototype of a three-phase, four-level NPC-based dc–ac converter.</p>
Full article ">Figure 16
<p>Experimental results under a ramp variation of the <span class="html-italic">v</span><sup>*</sup><sub>C2</sub> and <span class="html-italic">v</span><sup>*</sup><sub>C3</sub> commands of a four-level, three-phase system. Same conditions as in <a href="#electronics-13-02671-f009" class="html-fig">Figure 9</a>. (<b>a</b>) Control in [<a href="#B5-electronics-13-02671" class="html-bibr">5</a>] without decoupling. (<b>b</b>) Proposed inherently decoupled control from <a href="#electronics-13-02671-f003" class="html-fig">Figure 3</a>, equivalent to the control in [<a href="#B5-electronics-13-02671" class="html-bibr">5</a>] with decoupling.</p>
Full article ">
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