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Search Results (712)

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Keywords = WPT

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16 pages, 2919 KiB  
Article
Efficiency Optimization of LCL-Resonant Wireless Power Transfer Systems via Bidirectional Electromagnetic–Thermal Coupling Field Dynamics
by Yao Yuan, Yuan La, Sicheng Shen, Yihui Zhao, Jianchao Li and Fanghui Yin
Energies 2024, 17(17), 4507; https://doi.org/10.3390/en17174507 - 8 Sep 2024
Viewed by 543
Abstract
This paper delved into the thermal dynamics and stability of Wireless Power Transfer (WPT) systems, with a focus on the temperature effects on the coil structure. Using the Finite Element Method (FEM), this study investigated both unidirectional and bidirectional coupling field simulations, assessing [...] Read more.
This paper delved into the thermal dynamics and stability of Wireless Power Transfer (WPT) systems, with a focus on the temperature effects on the coil structure. Using the Finite Element Method (FEM), this study investigated both unidirectional and bidirectional coupling field simulations, assessing their impacts on the transmission efficiency of LCL-resonant WPT systems. The boundary conditions and processes of the electromagnetic–thermal coupling field related to coil loss were analyzed, as well as the dynamic thermal balance in the bidirectional coupling field model. It was found that there is a significant temperature variation across the coil, with the highest temperatures at the central position and the lowest at the edges. This temperature rise notably changed the electrical parameters of the system, leading to variations in its operating state and a reduction in transmission efficiency. A constant coil voltage control strategy was more effective in mitigating the temperature rise compared to a constant coil current strategy, providing valuable insight for enhancing the efficiency and stability of WPT systems. Full article
(This article belongs to the Section F1: Electrical Power System)
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Figure 1

Figure 1
<p>Simplified equivalent circuit of a WPT system using LCL resonance topology.</p>
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<p>PC40’s core loss and saturation magnetic flux vs. temperature characteristics.</p>
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<p>The dynamic coupling process of the WPT coil’s electromagnetic–thermal coupling field.</p>
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<p>The 3D view and the detailed layout of the simulated coil structure model.</p>
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<p>The prototype of the experimental platform of the simulated coil structure model.</p>
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<p>The electromagnetic–thermal unidirectional coupled field analysis process.</p>
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<p>The dynamic temperature rise process of the TX coil windings.</p>
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<p>The iteration process of the electromagnetic–thermal coupling field analysis.</p>
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<p>The temperature distribution field of the TX coil in the approximate thermal steady state in bidirectional coupling analysis, current source excitation.</p>
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<p>The dynamic process in unidirectional and bidirectional coupling analysis: (<b>a</b>) temperature rise in current source excitation; (<b>b</b>) temperature rise in voltage source excitation; (<b>c</b>) efficiency change of system; and (<b>d</b>) coil’s ohm loss change of system.</p>
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21 pages, 5233 KiB  
Review
One Health Ecological Approach to Sustainable Wireless Energy Transfer Aboard Electric Vehicles for Smart Cities
by Adel Razek
Energies 2024, 17(17), 4349; https://doi.org/10.3390/en17174349 - 30 Aug 2024
Viewed by 352
Abstract
This investigation is part of a topical situation where wireless equipment is gradually being used for energy transfer, particularly for autonomous systems and the use of decarbonized energies. A characteristic example of decarbonized autonomous use is linked to the substitution of thermal engine [...] Read more.
This investigation is part of a topical situation where wireless equipment is gradually being used for energy transfer, particularly for autonomous systems and the use of decarbonized energies. A characteristic example of decarbonized autonomous use is linked to the substitution of thermal engine vehicles for electric vehicles (EVs) equipped with energy storage batteries. This response was considered in an ecological context of reducing air pollution and defending planetary biodiversity, which are currently vital. These EVs ultimately operate thanks to the wireless charging of their batteries when stationary or running. By changing long-established means of transport that have become a threat to biodiversity, it is necessary to ensure that innovative replacement solutions protect this biodiversity. In addition, the construction of wireless power transfer (WPT) battery chargers for these EVs must offer an optimal ecology of clean energy saving. In such a context, the two concepts of One Health (OH) and Responsible Attitude (RA) will find their place in the design and control of WPT tools in EVs. This contribution aims to illustrate and analyze the roles of the green and non-wasteful OH and RA approaches in the design and control of WPT embedded in EVs for the smart city (SC) environment. In the paper, WPT tools are first introduced. The design and control of EV battery charging tools are then examined. The biological effects on living tissues due to the electromagnetic field (EMF) radiation of WPT are analyzed. The phenomena and equations governing the design of WPT and the effects of EMF radiation are then exposed. The OH and RA approaches in the SC context are afterward analyzed. The protection against the unsafe effects of WPT tools in the SC environment is consequently explored. The analyses followed in the paper are supported by examples from the literature. The explorations proposed in this contribution have made it possible to highlight certain notions, allowing a more in-depth understanding of the use of EVs with WPT rechargeable batteries for SCs. Thus, the analysis and fusion of these topics are at the heart of this contribution. Full article
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Figure 1
<p>Schematics of a compensated ICT in EV IPT.</p>
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<p>Summarized schematics of IPT between battery load and AC grid.</p>
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<p>A 3D Structure of an ICT including ground transmitter, EV bottom receiver coils, covered by 2 magnetic ferrites plates, and a steel chassis plate [<a href="#B25-energies-17-04349" class="html-bibr">25</a>].</p>
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<p>Relation of the B fields obtained from the two meta-models related to the FEM computations for three learning samples case [<a href="#B83-energies-17-04349" class="html-bibr">83</a>].</p>
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<p>Relation of the B fields obtained from the two meta-models related to the FEM computations for 15 learning samples case [<a href="#B83-energies-17-04349" class="html-bibr">83</a>].</p>
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<p>The error of B fields obtained from the Kriging meta-model related to the FEM function of the number of samples [<a href="#B83-energies-17-04349" class="html-bibr">83</a>].</p>
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<p>Illustrative examples of threatening situations for animals and plants due to IPT charging tools at the bottom of EVs.</p>
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<p>Illustrative examples of threatening situations for animals and plants due to IPT charging tools at the bottom of EVs.</p>
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<p>The causal approach of the design and energy expended in EV-IPT, its expected utility, and its unsolicited effects on humans and the environment.</p>
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<p>RA and OH approach through the design and use of clean energy in IPT counting whole SC biodiversity by monitoring of adverse EMF effects.</p>
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<p>High-resolution anatomical human body model with its different organs and tissues [<a href="#B59-energies-17-04349" class="html-bibr">59</a>].</p>
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<p>Distribution of induced fields in the body. (<b>a</b>) Magnitude of B (T), (<b>b</b>) Magnitude of E (V/m), for a 3 kW, 30 kHz IPT [<a href="#B59-energies-17-04349" class="html-bibr">59</a>].</p>
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<p>Summarized illustration of a matched monitoring of a complex procedure (EV-IPT-Battery connected to SC-Grid) with its virtual model [<a href="#B103-energies-17-04349" class="html-bibr">103</a>].</p>
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16 pages, 666 KiB  
Article
Energy-Efficient Hybrid Wireless Power Transfer Technique for Relay-Based IIoT Applications
by Vikash Singh, Roshan Kumar, Byomakesh Mahapatra and Chrompet Ramesh Srinivasan
Designs 2024, 8(5), 84; https://doi.org/10.3390/designs8050084 - 26 Aug 2024
Viewed by 470
Abstract
This paper introduces an innovative hybrid wireless power transfer (H-WPT) scheme tailored for IIoT networks employing multiple relay nodes. The scheme allows relay nodes to dynamically select their power source for energy harvesting based on real-time channel conditions. Our analysis evaluates outage probability [...] Read more.
This paper introduces an innovative hybrid wireless power transfer (H-WPT) scheme tailored for IIoT networks employing multiple relay nodes. The scheme allows relay nodes to dynamically select their power source for energy harvesting based on real-time channel conditions. Our analysis evaluates outage probability within decode-and-forward (DF) relaying and adaptive power splitting (APS) frameworks, while also considering the energy used by relay nodes for ACK signaling. A notable feature of the H-WPT scheme is its decentralized operation, enabling relay nodes to independently choose the optimal relay and power source using instantaneous channel gain. This approach conserves significant energy otherwise wasted in centralized control methods, where extensive information exchange is required. This conservation is particularly beneficial for energy-constrained sensor networks, significantly extending their operational lifetime. Numerical results demonstrate that the proposed hybrid approach significantly outperforms the traditional distance-based power source selection approach, without additional energy consumption or increased system complexity. The scheme’s efficient power management capabilities underscore its potential for practical applications in IIoT environments, where resource optimization is crucial. Full article
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Figure 1
<p>A relay network model.</p>
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<p>A relay network with one source, destination pair, and multiple relay nodes.</p>
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<p>Adaptive power splitting protocol.</p>
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<p>A caption describing the overall figure. (<b>a</b>) Destination-based wireless power transfer scheme (DWPT). (<b>b</b>) Source-based wireless power transfer scheme (SWPT).</p>
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<p>Outage probability versus the <math display="inline"><semantics> <msub> <mi>d</mi> <mn>1</mn> </msub> </semantics></math>. Parameters: <math display="inline"><semantics> <mrow> <mi mathvariant="sans-serif">R</mi> <mo>=</mo> <mn>3</mn> </mrow> </semantics></math>, <math display="inline"><semantics> <mrow> <mi>ζ</mi> <mo>=</mo> <mn>0.8</mn> </mrow> </semantics></math>, <math display="inline"><semantics> <mrow> <msubsup> <mi>σ</mi> <mi>D</mi> <mn>2</mn> </msubsup> <mo>=</mo> <mo>−</mo> <mn>70</mn> </mrow> </semantics></math> dBm, <math display="inline"><semantics> <mrow> <msub> <mi>P</mi> <mi>A</mi> </msub> <mo>=</mo> <mo>−</mo> <mn>50</mn> </mrow> </semantics></math> dBm, <math display="inline"><semantics> <mrow> <mi>M</mi> <mo>=</mo> <mn>4</mn> </mrow> </semantics></math>, and <math display="inline"><semantics> <mrow> <msub> <mi>P</mi> <mn>0</mn> </msub> <mo>=</mo> <mn>3</mn> </mrow> </semantics></math> dBm.</p>
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<p>Outage probability versus <math display="inline"><semantics> <msub> <mi>d</mi> <mn>1</mn> </msub> </semantics></math>. Parameters: <math display="inline"><semantics> <mrow> <mi mathvariant="sans-serif">R</mi> <mo>=</mo> <mn>3</mn> </mrow> </semantics></math>, <math display="inline"><semantics> <mrow> <mi>ζ</mi> <mo>=</mo> <mn>0.8</mn> </mrow> </semantics></math>, <math display="inline"><semantics> <mrow> <msubsup> <mi>σ</mi> <mi>D</mi> <mn>2</mn> </msubsup> <mo>=</mo> <mo>−</mo> <mn>70</mn> </mrow> </semantics></math> dBm, <math display="inline"><semantics> <mrow> <msub> <mi>P</mi> <mi>A</mi> </msub> <mo>=</mo> <mo>−</mo> <mn>50</mn> </mrow> </semantics></math> dBm, <math display="inline"><semantics> <mrow> <mi>M</mi> <mo>=</mo> <mn>4</mn> </mrow> </semantics></math>, and <math display="inline"><semantics> <mrow> <msub> <mi>P</mi> <mn>0</mn> </msub> <mo>=</mo> <mn>5</mn> </mrow> </semantics></math> dBm.</p>
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<p>Outage probability versus <math display="inline"><semantics> <msub> <mi>d</mi> <mn>1</mn> </msub> </semantics></math>. Parameters: <math display="inline"><semantics> <mrow> <mi mathvariant="sans-serif">R</mi> <mo>=</mo> <mn>3</mn> </mrow> </semantics></math>, <math display="inline"><semantics> <mrow> <mi>ζ</mi> <mo>=</mo> <mn>0.8</mn> </mrow> </semantics></math>, <math display="inline"><semantics> <mrow> <msubsup> <mi>σ</mi> <mi>D</mi> <mn>2</mn> </msubsup> <mo>=</mo> <mo>−</mo> <mn>70</mn> </mrow> </semantics></math> dBm, <math display="inline"><semantics> <mrow> <msub> <mi>P</mi> <mi>A</mi> </msub> <mo>=</mo> <mo>−</mo> <mn>50</mn> </mrow> </semantics></math> dBm, and <math display="inline"><semantics> <mrow> <msub> <mi>P</mi> <mn>0</mn> </msub> <mo>=</mo> <mn>5</mn> </mrow> </semantics></math> dBm.</p>
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<p>Outage probability versus <math display="inline"><semantics> <msub> <mi>d</mi> <mn>1</mn> </msub> </semantics></math>. Parameters: <math display="inline"><semantics> <mrow> <mi mathvariant="sans-serif">R</mi> <mo>=</mo> <mn>3</mn> </mrow> </semantics></math>, <math display="inline"><semantics> <mrow> <mi>ζ</mi> <mo>=</mo> <mn>0.8</mn> </mrow> </semantics></math>, <math display="inline"><semantics> <mrow> <msubsup> <mi>σ</mi> <mi>D</mi> <mn>2</mn> </msubsup> <mo>=</mo> <mo>−</mo> <mn>70</mn> </mrow> </semantics></math> dBm, <math display="inline"><semantics> <mrow> <mi>M</mi> <mo>=</mo> <mn>8</mn> </mrow> </semantics></math>, and <math display="inline"><semantics> <mrow> <msub> <mi>P</mi> <mn>0</mn> </msub> <mo>=</mo> <mn>5</mn> </mrow> </semantics></math> dBm.</p>
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23 pages, 9045 KiB  
Article
Addressing EMI and EMF Challenges in EV Wireless Charging with the Alternating Voltage Phase Coil
by Zeeshan Shafiq, Tong Li, Jinglin Xia, Siqi Li, Xi Yang and Yu Zhao
Actuators 2024, 13(9), 324; https://doi.org/10.3390/act13090324 - 26 Aug 2024
Viewed by 448
Abstract
Wireless charging technologies are widely used in electric vehicles (EVs) due to their advantages of convenience and safety. Conventional wireless charging systems often use planar circular or square spiral windings, which tend to produce strong electric fields (E-fields), leading to electromagnetic interference (EMI) [...] Read more.
Wireless charging technologies are widely used in electric vehicles (EVs) due to their advantages of convenience and safety. Conventional wireless charging systems often use planar circular or square spiral windings, which tend to produce strong electric fields (E-fields), leading to electromagnetic interference (EMI) and potential health risks. These standard coil configurations, while efficient in energy transfer, often fail to address the critical balance between E-field emission reduction and power transfer effectiveness. This study presents an “Alternating Voltage Phase Coil” (AVPC), an innovative coil design that can address these limitations. The AVPC retains the standard dimensions of traditional square coils (400 mm in length and width, with a 2.5 mm wire diameter and 22 turns), but introduces a novel current flow pattern called Sequential Inversion Winding (SIW). This configuration of the winding significantly reduces E-field emissions by altering the sequence of current through its loops. Rigorous simulations and experimental evaluations have demonstrated the AVPC’s ability to lower E-field emissions by effectively up to 85% while maintaining charging power. Meeting stringent regulatory standards, this advancement in the proposed coil design method provides a way for WPT systems to meet stringent regulatory standards requirements while maintaining transmission capability. Full article
(This article belongs to the Special Issue Power Electronics and Actuators)
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Figure 1
<p>General wireless power transfer charging system for EVs.</p>
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<p>Structure of the coil prototype. (<b>a</b>) Traditional coil. (<b>b</b>) AVPC 1. (<b>c</b>) AVPC 2.</p>
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<p>E-field mitigation in wireless charging systems. (<b>a</b>) Optimized coil design. (<b>b</b>) Spice circuit of traditional coil. (<b>c</b>) Spice circuit of the AVPC.</p>
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<p>Coil Parameter. (<b>a</b>) Inductance. (<b>b</b>) Coupling coefficient.</p>
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<p>Coil wave forms. (<b>a</b>) Traditional coil. (<b>b</b>) AVPC.</p>
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<p>Comparative E-field distributions in coil designs without environmental effects. (<b>a</b>) Traditional coil side view. (<b>b</b>) AVPC 1 side view. (<b>c</b>) AVPC 2 side view. (<b>d</b>) Traditional coil top view. (<b>e</b>) AVPC 1 top view. (<b>f</b>) AVPC 2 top view. (<b>g</b>) Traditional coil side view vector distribution. (<b>h</b>) AVPC 1 side view vector distribution. (<b>i</b>) AVPC 2 side view vector distribution.</p>
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<p>E−field intensity comparison at measurement points at 100 mm distance at Z axis. (<b>a</b>) E−Field Intensity in Pristine Conditions (<b>b</b>) E-Field Intensity Amidst Foreign Metal Interference.</p>
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<p>Comparison E-field distribution with a conductive aluminum plate at 100 mm distance. (<b>a</b>) Traditional coil side view. (<b>b</b>) AVPC 1 side view. (<b>c</b>) AVPC 2 side view. (<b>d</b>) Traditional coil top view. (<b>e</b>) AVPC 1 top view. (<b>f</b>) AVPC 2 top view. (<b>g</b>) Traditional coil side view vector distribution. (<b>h</b>) AVPC 1 side view vector distribution. (<b>i</b>) AVPC 2 side view vector distribution.</p>
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<p>Comparison of the H-Field in the design coil paid. (<b>a</b>) Traditional coil side view. (<b>b</b>) AVPC 1 side view. (<b>c</b>) AVPC 2 side view. (<b>d</b>) Traditional coil top view. (<b>e</b>) AVPC 1 top view. (<b>f</b>) AVPC 2 top view. (<b>g</b>) Traditional coil side view vector distribution. (<b>h</b>) AVPC 1 side view vector distribution. (<b>i</b>) AVPC 2 side view vector distribution.</p>
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<p>Comparative analysis of electromagnetic radiation distributions in innovative coil designs. (<b>a</b>) Traditional coil. (<b>b</b>) AVPC 1. (<b>c</b>) AVPC 2.</p>
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<p>Shows experimental setup illustrating LCC compensation network and measurement apparatus. (<b>a</b>) Show distance between coil and the measuring points. (<b>b</b>) Experimental setup and equipment’s.</p>
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<p>Measurement E-field emission comparisons across coil designs. (<b>a</b>) Traditional coil. (<b>b</b>) AVPC 1. (<b>c</b>) AVPC 2.</p>
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<p>Comparative visualization of E−field intensity reduction across coil designs in EV charging applications.</p>
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<p>Average electric field intensities comparison.</p>
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17 pages, 4358 KiB  
Article
A Dual Constant Current Output Ports WPT System Based on Integrated Coil Decoupling: Analysis, Design, and Verification
by Le Yu, Shujia Xu, Jiabin Wang, Lin Yang and Xuebin Zhou
Electronics 2024, 13(17), 3371; https://doi.org/10.3390/electronics13173371 - 25 Aug 2024
Viewed by 412
Abstract
With the high integration of power electronic devices, wireless power transfer (WPT) systems are required to have output characteristics of different specifications that are independent of the load. However, existing methods for realizing dual-output WPT systems have problems such as complex circuits, cumbersome [...] Read more.
With the high integration of power electronic devices, wireless power transfer (WPT) systems are required to have output characteristics of different specifications that are independent of the load. However, existing methods for realizing dual-output WPT systems have problems such as complex circuits, cumbersome control schemes, low system stability, insufficient system space utilization, and unnecessary cross-coupling. Therefore, in order to solve the above problems, this paper proposes a dual-receiver WPT system with dual constant current (CC) output based on an integrated decoupling coil. In this system, the DD coil is wound vertically in series with the solenoid coil and serves as the first receiving coil to achieve energy transmission in the system. While the solenoid coil is used in the transmitting coil and the second receiving coil, and the coils are perpendicular to each other to achieve natural decoupling. Furthermore, the receiving coils are integrated together on the receiving side ferrite plate. Therefore, there is no cross-coupling interference in the system, which simplifies the system design. Firstly, the natural decoupling characteristics of the magnetic coupler and the coil optimization method are analyzed in detail theoretically. Secondly, a detailed mathematical analysis is performed on the dual CC output characteristics with different specifications that are load-independent and have zero phase angle operation. Again, the zero voltage switching of the inverter can be achieved by changing the compensation component parameters through simulation verification. Finally, a prototype with a rated power of 283 W is constructed for validation purposes. The first receiver delivers a CC output of 3 A, while the second receiver provides a CC output of 4 A, with the DC–DC conversion efficiency reaching a peak of 90.2%. The experimental results confirm the accuracy of the theoretical analysis. Full article
(This article belongs to the Special Issue New Insights in Power Electronics: Prospects and Challenges)
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Figure 1

Figure 1
<p>Distribution of magnetic flux in two solenoid coils oriented perpendicularly to each other.</p>
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<p>Schematic diagram of the magnetic flux distribution of two perpendicular DD coils and a solenoid coil.</p>
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<p>Proposed magnetic coupler structure and optimization method.</p>
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<p>The schematic diagram of magnetic coupling for the magnetic coupler.</p>
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<p>Overall architecture of the proposed WPT system based on integrated decoupling coils.</p>
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<p>Equivalent circuit diagram of the WPT system.</p>
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<p>Frequency sweep curves of a dual−output WPT system under different loads. (<b>a</b>) Output current of the first receiver. (<b>b</b>) Output current of the second receiver. (<b>c</b>) Input impedance angle.</p>
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<p>Normalized capacitor <math display="inline"><semantics> <msub> <mi>C</mi> <mrow> <mi>P</mi> <mi>t</mi> </mrow> </msub> </semantics></math> and <math display="inline"><semantics> <msub> <mi>R</mi> <mrow> <mi>B</mi> <mn>1</mn> </mrow> </msub> </semantics></math> and (<b>a</b>) output current, (<b>c</b>) input phase. Normalized capacitor <math display="inline"><semantics> <msub> <mi>C</mi> <mrow> <mi>P</mi> <mi>t</mi> </mrow> </msub> </semantics></math> and <math display="inline"><semantics> <msub> <mi>R</mi> <mrow> <mi>B</mi> <mn>2</mn> </mrow> </msub> </semantics></math> and (<b>b</b>) output current, (<b>d</b>) input phase angle.</p>
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<p>Normalized capacitor <math display="inline"><semantics> <msub> <mi>C</mi> <mrow> <mi>S</mi> <mi>t</mi> </mrow> </msub> </semantics></math> and <math display="inline"><semantics> <msub> <mi>R</mi> <mrow> <mi>B</mi> <mn>1</mn> </mrow> </msub> </semantics></math> and (<b>a</b>) output current, (<b>c</b>) input phase. Normalized capacitor <math display="inline"><semantics> <msub> <mi>C</mi> <mrow> <mi>S</mi> <mi>t</mi> </mrow> </msub> </semantics></math> and <math display="inline"><semantics> <msub> <mi>R</mi> <mrow> <mi>B</mi> <mn>2</mn> </mrow> </msub> </semantics></math> and (<b>b</b>) output current, (<b>d</b>) input phase angle.</p>
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<p>Normalized capacitor <math display="inline"><semantics> <msub> <mi>C</mi> <mrow> <mi>T</mi> <mi>t</mi> </mrow> </msub> </semantics></math> and <math display="inline"><semantics> <msub> <mi>R</mi> <mrow> <mi>B</mi> <mn>1</mn> </mrow> </msub> </semantics></math> and (<b>a</b>) output current, (<b>c</b>) input phase. Normalized capacitor <math display="inline"><semantics> <msub> <mi>C</mi> <mrow> <mi>T</mi> <mi>t</mi> </mrow> </msub> </semantics></math> and <math display="inline"><semantics> <msub> <mi>R</mi> <mrow> <mi>B</mi> <mn>2</mn> </mrow> </msub> </semantics></math> and (<b>b</b>) output current, (<b>d</b>) input phase angle.</p>
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<p>Normalized capacitor <math display="inline"><semantics> <msub> <mi>C</mi> <mrow> <mn>1</mn> <mi>t</mi> </mrow> </msub> </semantics></math> and <math display="inline"><semantics> <msub> <mi>R</mi> <mrow> <mi>B</mi> <mn>1</mn> </mrow> </msub> </semantics></math> and (<b>a</b>) output current, (<b>c</b>) input phase. Normalized capacitor <math display="inline"><semantics> <msub> <mi>C</mi> <mrow> <mn>1</mn> <mi>t</mi> </mrow> </msub> </semantics></math> and <math display="inline"><semantics> <msub> <mi>R</mi> <mrow> <mi>B</mi> <mn>2</mn> </mrow> </msub> </semantics></math> and (<b>b</b>) output current, (<b>d</b>) input phase angle.</p>
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<p>Normalized capacitor <math display="inline"><semantics> <msub> <mi>L</mi> <mrow> <mn>1</mn> <mi>t</mi> </mrow> </msub> </semantics></math> and <math display="inline"><semantics> <msub> <mi>R</mi> <mrow> <mi>B</mi> <mn>1</mn> </mrow> </msub> </semantics></math> and (<b>a</b>) output current, (<b>c</b>) input phase. Normalized capacitor <math display="inline"><semantics> <msub> <mi>L</mi> <mrow> <mn>1</mn> <mi>t</mi> </mrow> </msub> </semantics></math> and <math display="inline"><semantics> <msub> <mi>R</mi> <mrow> <mi>B</mi> <mn>2</mn> </mrow> </msub> </semantics></math> and (<b>b</b>) output current, (<b>d</b>) input phase angle.</p>
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<p>Proposed magnetic coupler structure.</p>
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<p>Constructed verification experimental prototype.</p>
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<p>Experimental waveforms of <math display="inline"><semantics> <msub> <mi mathvariant="bold-italic">U</mi> <mrow> <mi>i</mi> <mi>n</mi> </mrow> </msub> </semantics></math>, <math display="inline"><semantics> <msub> <mi mathvariant="bold-italic">I</mi> <mi>P</mi> </msub> </semantics></math>, <math display="inline"><semantics> <msub> <mi>I</mi> <mrow> <mi>B</mi> <mn>1</mn> </mrow> </msub> </semantics></math>, and <math display="inline"><semantics> <msub> <mi>I</mi> <mrow> <mi>B</mi> <mn>2</mn> </mrow> </msub> </semantics></math> under ZPA conditions (<b>a</b>) <math display="inline"><semantics> <msub> <mi>R</mi> <mrow> <mi>B</mi> <mn>1</mn> </mrow> </msub> </semantics></math> = 5 <math display="inline"><semantics> <mi mathvariant="normal">Ω</mi> </semantics></math>, <math display="inline"><semantics> <msub> <mi>R</mi> <mrow> <mi>B</mi> <mn>2</mn> </mrow> </msub> </semantics></math> = 10 <math display="inline"><semantics> <mi mathvariant="normal">Ω</mi> </semantics></math>, (<b>b</b>) <math display="inline"><semantics> <msub> <mi>R</mi> <mrow> <mi>B</mi> <mn>1</mn> </mrow> </msub> </semantics></math> = 10 <math display="inline"><semantics> <mi mathvariant="normal">Ω</mi> </semantics></math>, <math display="inline"><semantics> <msub> <mi>R</mi> <mrow> <mi>B</mi> <mn>1</mn> </mrow> </msub> </semantics></math> = 15 <math display="inline"><semantics> <mi mathvariant="normal">Ω</mi> </semantics></math>.</p>
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<p>Experimental waveforms of <math display="inline"><semantics> <msub> <mi mathvariant="bold-italic">U</mi> <mrow> <mi>i</mi> <mi>n</mi> </mrow> </msub> </semantics></math>, <math display="inline"><semantics> <msub> <mi mathvariant="bold-italic">I</mi> <mi>P</mi> </msub> </semantics></math>, <math display="inline"><semantics> <msub> <mi>I</mi> <mrow> <mi>B</mi> <mn>1</mn> </mrow> </msub> </semantics></math> and <math display="inline"><semantics> <msub> <mi>I</mi> <mrow> <mi>B</mi> <mn>2</mn> </mrow> </msub> </semantics></math> under ZVS conditions (<b>a</b>) <math display="inline"><semantics> <msub> <mi>R</mi> <mrow> <mi>B</mi> <mn>1</mn> </mrow> </msub> </semantics></math> = 5 <math display="inline"><semantics> <mi mathvariant="normal">Ω</mi> </semantics></math>, <math display="inline"><semantics> <msub> <mi>R</mi> <mrow> <mi>B</mi> <mn>2</mn> </mrow> </msub> </semantics></math> = 10 <math display="inline"><semantics> <mi mathvariant="normal">Ω</mi> </semantics></math>, (<b>b</b>) <math display="inline"><semantics> <msub> <mi>R</mi> <mrow> <mi>B</mi> <mn>1</mn> </mrow> </msub> </semantics></math> = 10 <math display="inline"><semantics> <mi mathvariant="normal">Ω</mi> </semantics></math>, <math display="inline"><semantics> <msub> <mi>R</mi> <mrow> <mi>B</mi> <mn>1</mn> </mrow> </msub> </semantics></math> = 15 <math display="inline"><semantics> <mi mathvariant="normal">Ω</mi> </semantics></math>.</p>
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<p>Total DC-DC efficiency surface under different load combinations.</p>
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<p>Power Distribution Ratio Surface (<b>a</b>) The power distribution ratio of the first receiver, (<b>b</b>) The power distribution ratio of the second receiver.</p>
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<p>Power loss distribution of each system component measured under aligned conditions with a load resistor <math display="inline"><semantics> <msub> <mi>R</mi> <mrow> <mi>B</mi> <mn>1</mn> </mrow> </msub> </semantics></math> of 5 <math display="inline"><semantics> <mi mathvariant="normal">Ω</mi> </semantics></math> and load resistor <math display="inline"><semantics> <msub> <mi>R</mi> <mrow> <mi>B</mi> <mn>1</mn> </mrow> </msub> </semantics></math> of 19 <math display="inline"><semantics> <mi mathvariant="normal">Ω</mi> </semantics></math>.</p>
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15 pages, 4222 KiB  
Article
Array of Active Shielding Coils for Magnetic Field Mitigation in Automotive Wireless Power Transfer Systems
by Silvano Cruciani, Tommaso Campi, Francesca Maradei and Mauro Feliziani
Energies 2024, 17(17), 4233; https://doi.org/10.3390/en17174233 - 24 Aug 2024
Viewed by 427
Abstract
This paper deals with the mitigation of magnetic field levels produced by a wireless power transfer (WPT) system to recharge the battery of an electric vehicle (EV). In this work, an array of active coils surrounding the WPT coils is proposed as a [...] Read more.
This paper deals with the mitigation of magnetic field levels produced by a wireless power transfer (WPT) system to recharge the battery of an electric vehicle (EV). In this work, an array of active coils surrounding the WPT coils is proposed as a mitigation technique. The theory and new methodological aspects are the focus of the paper. Magnetic field levels in the environment are calculated numerically without and with the presence of an array of active coils in a stationary WPT system for automotive applications. By the proposed mitigation method, the field levels beside the vehicle are significantly reduced and comply with the reference levels (RLs) of the ICNIRP 2010 guidelines for human exposure to electromagnetic fields and the magnetic flux density limits proposed by ISO 14117 for electromagnetic interference (EMI) in cardiac implantable electronic devices (CIEDs). Full article
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<p>Equivalent circuit of a WPT system in the presence of <span class="html-italic">N</span> − 2 shielding coils.</p>
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<p>Equivalent simplified circuit of a WPT system LCC compensation and <span class="html-italic">N</span> − 2 active shielding coils.</p>
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<p>Electro-geometrical configuration of the GA coil.</p>
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<p>Electro-geometrical configuration of the VA coil.</p>
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<p>Proposed active shielding coil configuration: 2 coils (<b>a</b>), 4 coils (<b>b</b>), and 6 coils (<b>c</b>).</p>
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<p>Proposed active shielding coil configuration: 2 coils (<b>a</b>), 4 coils (<b>b</b>), and 6 coils (<b>c</b>).</p>
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<p>Surfaces <span class="html-italic">S</span><sub>1</sub> and <span class="html-italic">S</span><sub>2</sub> beside the WPT coil configuration where the average magnetic flux induction is calculated.</p>
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<p>Volumes beside the WPT coil configuration where the magnetic flux induction is calculated.</p>
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<p>Distribution of the magnetic flux density <span class="html-italic">B</span> (rms) in the volumes without active shielding (<b>a</b>), with 2 active shielding coils (<b>b</b>), with 4 active shielding coils (<b>c</b>), and with 6 active shielding coils (<b>d</b>).</p>
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<p>Distribution of the magnetic flux density <span class="html-italic">B</span> (rms) in the volumes without active shielding (<b>a</b>), with 2 active shielding coils (<b>b</b>), with 4 active shielding coils (<b>c</b>), and with 6 active shielding coils (<b>d</b>).</p>
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16 pages, 2312 KiB  
Article
Enhanced Scattering by Wearable Objects in Wireless Power Transfer Links: Case Studies
by Ludovica Tognolatti, Cristina Ponti and Giuseppe Schettini
Mathematics 2024, 12(17), 2606; https://doi.org/10.3390/math12172606 - 23 Aug 2024
Viewed by 396
Abstract
Wireless power transfer (WPT) systems have ushered in a new era for wearable and implantable technologies, introducing opportunities for enhanced device functionality. A pivotal aspect in improving these devices is the optimization of electromagnetic transmission. This paper presents several solutions to improve electromagnetic [...] Read more.
Wireless power transfer (WPT) systems have ushered in a new era for wearable and implantable technologies, introducing opportunities for enhanced device functionality. A pivotal aspect in improving these devices is the optimization of electromagnetic transmission. This paper presents several solutions to improve electromagnetic transmission to an implantable/wearable device. Several scatterers are considered to mimic objects that can be easily worn by a patient, such as necklaces and bracelets, or easily integrated into textile fabric. An analytical method is employed to address the scattering by cylindrical objects above a biological tissue, modeled as a multilayer. Expansions into cylindrical waves, also represented through plane-wave spectra, are used to express the scattered fields in each medium. Numerical results for both the case of conducting and of dielectric cylindrical scatterers are presented at a frequency of the Industrial, Scientific and Medical band (f=2.45 GHz), showing possible configurations of worn objects for electromagnetic field intensification. Full article
(This article belongs to the Special Issue Analytical Methods in Wave Scattering and Diffraction, 2nd Edition)
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<p>Geometry of the scattering problem.</p>
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<p>Geometry of the scattering problem in a WPT system.</p>
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<p>Reflection coefficient for TM and TE polarization for: (<b>a</b>) cylindrical scatterer and (<b>b</b>) unit cell with rectangular scatterer (continuous case).</p>
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<p>Configuration with <math display="inline"><semantics> <mrow> <mi>N</mi> <mo>=</mo> <mn>3</mn> </mrow> </semantics></math> dielectric cylindrical scatterers of radius <math display="inline"><semantics> <msub> <mi>r</mi> <mn>0</mn> </msub> </semantics></math>, <math display="inline"><semantics> <msub> <mi>r</mi> <mn>1</mn> </msub> </semantics></math>, and <math display="inline"><semantics> <msub> <mi>r</mi> <mn>2</mn> </msub> </semantics></math> and spaced by a gap. The thicknesses of the layers are: <math display="inline"><semantics> <mrow> <msub> <mi>d</mi> <mn>1</mn> </msub> <mo>=</mo> <mn>0.8</mn> </mrow> </semantics></math> mm, <math display="inline"><semantics> <mrow> <msub> <mi>d</mi> <mn>2</mn> </msub> <mo>=</mo> <mn>3</mn> </mrow> </semantics></math> mm, <math display="inline"><semantics> <mrow> <msub> <mi>d</mi> <mn>3</mn> </msub> <mo>=</mo> <mn>10</mn> </mrow> </semantics></math> mm, <math display="inline"><semantics> <mrow> <msub> <mi>d</mi> <mn>4</mn> </msub> <mo>=</mo> <mn>2</mn> </mrow> </semantics></math> mm.</p>
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<p>(<b>a</b>) Magnitude of the electric field evaluated at <math display="inline"><semantics> <mrow> <mi>x</mi> <mo>=</mo> <mn>13.8</mn> </mrow> </semantics></math> mm as the radius of the scatterer varies and for different gap values; (<b>b</b>) Horizontal profile of the electric field along <span class="html-italic">z</span> at <math display="inline"><semantics> <mrow> <mi>x</mi> <mo>=</mo> <mn>13.8</mn> </mrow> </semantics></math> mm for several radius values.</p>
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<p>(<b>a</b>) Electric field map (<b>b</b>) Vertical profile of the electric field along the multilayer structure. Comparison between the case where scatterers are present and the case where they are absent.</p>
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<p>Configurations in which an increased number of cylindrical scatterers are considered: (<b>a</b>) <math display="inline"><semantics> <mrow> <mi>N</mi> <mo>=</mo> <mn>10</mn> </mrow> </semantics></math>, (<b>c</b>) <math display="inline"><semantics> <mrow> <mi>N</mi> <mo>=</mo> <mn>15</mn> </mrow> </semantics></math>. (<b>b</b>,<b>d</b>) show the horizontal profile of the electric field at <math display="inline"><semantics> <mrow> <mi>x</mi> <mo>=</mo> <mn>13.8</mn> </mrow> </semantics></math> mm, for the two configurations, respectively.</p>
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<p>Configuration with <math display="inline"><semantics> <mrow> <mi>N</mi> <mo>=</mo> <mn>5</mn> </mrow> </semantics></math> dielectric cylinders (<math display="inline"><semantics> <mrow> <msub> <mi>ε</mi> <mi>r</mi> </msub> <mo>=</mo> <mn>10</mn> </mrow> </semantics></math>), with the same radii (<math display="inline"><semantics> <mrow> <msub> <mi>r</mi> <mn>0</mn> </msub> <mo>=</mo> <msub> <mi>r</mi> <mn>1</mn> </msub> <mo>=</mo> <msub> <mi>r</mi> <mn>2</mn> </msub> <mo>=</mo> <msub> <mi>r</mi> <mn>3</mn> </msub> <mo>=</mo> <msub> <mi>r</mi> <mn>4</mn> </msub> <mo>=</mo> <mn>9</mn> </mrow> </semantics></math> mm), positioned above a layer of skin, fat, muscle, and a layer mimicking a tumor inclusion (of thickness <math display="inline"><semantics> <mrow> <mi>h</mi> <mo>=</mo> <mn>6</mn> </mrow> </semantics></math> mm).</p>
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<p>Vertical profile of the electric field along the multilayer structure. Comparison between the case where scatterers are present and the case where they are absent for the configuration of <a href="#mathematics-12-02606-f008" class="html-fig">Figure 8</a>.</p>
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<p>(<b>a</b>) Horizontal profile of the electric field at <math display="inline"><semantics> <mrow> <mi>x</mi> <mo>=</mo> <mn>5</mn> </mrow> </semantics></math> mm for the configuration of <a href="#mathematics-12-02606-f008" class="html-fig">Figure 8</a>; (<b>b</b>) Electric field map at <math display="inline"><semantics> <mrow> <mi>f</mi> <mo>=</mo> <mn>2.45</mn> </mrow> </semantics></math> GHz.</p>
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<p>Configuration with <math display="inline"><semantics> <mrow> <mi>N</mi> <mo>=</mo> <mn>3</mn> </mrow> </semantics></math> dielectric cylinders (<math display="inline"><semantics> <mrow> <msub> <mi>ε</mi> <mi>r</mi> </msub> <mo>=</mo> <mn>10</mn> </mrow> </semantics></math>), with the same radii (<math display="inline"><semantics> <mrow> <msub> <mi>r</mi> <mn>0</mn> </msub> <mo>=</mo> <msub> <mi>r</mi> <mn>1</mn> </msub> <mo>=</mo> <msub> <mi>r</mi> <mn>2</mn> </msub> <mo>=</mo> <mn>9</mn> </mrow> </semantics></math> mm), positioned above a layer of skin, fat, muscle, and a layer mimicking a tumoral inclusion (of thickness <math display="inline"><semantics> <mrow> <mi>h</mi> <mo>=</mo> <mn>6</mn> </mrow> </semantics></math> mm).</p>
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<p>Vertical profile of the electric field along the multilayer structure. Comparison between the case where scatterers are present and the case where they are absent for the configuration of <a href="#mathematics-12-02606-f011" class="html-fig">Figure 11</a>.</p>
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<p>(<b>a</b>) Horizontal profile of the electric field at <math display="inline"><semantics> <mrow> <mi>x</mi> <mo>=</mo> <mn>5</mn> </mrow> </semantics></math> mm for the configuration of <a href="#mathematics-12-02606-f011" class="html-fig">Figure 11</a>; (<b>b</b>) Electric field map at <math display="inline"><semantics> <mrow> <mi>f</mi> <mo>=</mo> <mn>2.45</mn> </mrow> </semantics></math> GHz.</p>
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<p>Comparison between the analytical method CWA and CST: (<b>a</b>) Horizontal profile of the magnetic field at a depth of <math display="inline"><semantics> <mrow> <mi>x</mi> <mo>=</mo> <mn>1</mn> </mrow> </semantics></math> mm; (<b>b</b>) vertical profile of the magnetic field along the multilayer, <math display="inline"><semantics> <mrow> <mi>z</mi> <mo>=</mo> <mn>0</mn> </mrow> </semantics></math> mm.</p>
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<p>Comparison between the analytical method CWA and CST: (<b>a</b>) Horizontal profile of the magnetic field at a depth of <math display="inline"><semantics> <mrow> <mi>x</mi> <mo>=</mo> <mn>1</mn> </mrow> </semantics></math> mm; (<b>b</b>) vertical profile of the magnetic field along the multilayer, <math display="inline"><semantics> <mrow> <mi>z</mi> <mo>=</mo> <mn>0</mn> </mrow> </semantics></math> mm.</p>
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<p><span class="html-italic">N</span> metallic cylinders (perfectly electric conductor, PEC) placed above the multilayer.</p>
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<p>(<b>a</b>) Unit cell with PEC scatterer placed above the multilayer; (<b>b</b>) Reflection coefficient as a function of the dielectric constant of the matching layer.</p>
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<p>Reflection coefficient of the unit cell. (<b>a</b>) Comparison between no scatterer + no layer and scatterer + layer configurations; (<b>b</b>) Vertical profile of the electric field along the multilayer at <math display="inline"><semantics> <mrow> <mi>f</mi> <mo>=</mo> <mn>2.45</mn> </mrow> </semantics></math> GHz.</p>
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<p>(<b>a</b>) Configuration with <span class="html-italic">N</span> conducting cylindrical scatterers; (<b>b</b>) Horizontal profile of the electric field in the middle of the skin layer at <math display="inline"><semantics> <mrow> <mi>f</mi> <mo>=</mo> <mn>2.45</mn> </mrow> </semantics></math> GHz, for <math display="inline"><semantics> <mrow> <mi>N</mi> <mo>=</mo> <mn>7</mn> <mo>,</mo> <mn>15</mn> <mo>,</mo> <mn>23</mn> <mo>,</mo> <mn>29</mn> </mrow> </semantics></math>.</p>
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<p>Configuration with <math display="inline"><semantics> <mrow> <mi>N</mi> <mo>=</mo> <mn>7</mn> </mrow> </semantics></math> conducting cylindrical scatterers placed above a layer of cotton (<math display="inline"><semantics> <mrow> <msub> <mi>ε</mi> <mi>r</mi> </msub> <mo>=</mo> <mn>1.7</mn> </mrow> </semantics></math>), skin, fat, and muscle (<math display="inline"><semantics> <mrow> <msub> <mi>d</mi> <mn>1</mn> </msub> <mo>=</mo> <mn>2</mn> </mrow> </semantics></math> mm, <math display="inline"><semantics> <mrow> <msub> <mi>d</mi> <mn>2</mn> </msub> <mo>=</mo> <mn>0.8</mn> </mrow> </semantics></math> mm, <math display="inline"><semantics> <mrow> <msub> <mi>d</mi> <mn>3</mn> </msub> <mo>=</mo> <mn>3</mn> </mrow> </semantics></math> mm). Outer cylinders have radius <math display="inline"><semantics> <mrow> <mi>r</mi> <mo>=</mo> <mn>10</mn> </mrow> </semantics></math> mm; the inner one has a radius of <math display="inline"><semantics> <mrow> <mi>r</mi> <mo>=</mo> <mn>2</mn> </mrow> </semantics></math> mm.</p>
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<p>(<b>a</b>) Horizontal profile of the magnetic field in the middle of the cotton layer; (<b>b</b>) Horizontal profile of the electric field in the middle of the skin layer at <math display="inline"><semantics> <mrow> <mi>f</mi> <mo>=</mo> <mn>2.45</mn> </mrow> </semantics></math> GHz.</p>
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17 pages, 368 KiB  
Article
An Approach for Maximizing Computation Bits in UAV-Assisted Wireless Powered Mobile Edge Computing Networks
by Zhenbo Liu, Yunge Duan and Shuang Fu
Information 2024, 15(8), 503; https://doi.org/10.3390/info15080503 - 21 Aug 2024
Viewed by 448
Abstract
With the development of the Internet of Things (IoT), IoT nodes with limited energy and computing capability are no longer able to address increasingly complex computational tasks. To address this issue, an Unmanned Aerial Vehicle (UAV)-assisted Wireless Power Transfer (WPT) Mobile Edge Computing [...] Read more.
With the development of the Internet of Things (IoT), IoT nodes with limited energy and computing capability are no longer able to address increasingly complex computational tasks. To address this issue, an Unmanned Aerial Vehicle (UAV)-assisted Wireless Power Transfer (WPT) Mobile Edge Computing (MEC) system is proposed in this study. By jointly optimizing variables such as energy harvesting time, user transmission power, user offloading time, CPU frequency, and UAV deployment location, the system aims to maximize the number of computation bits by the users. This optimization yields a challenging non-convex optimization problem. To address these issues, a two-stage alternating method based on the Lagrangian dual method and the Successive Convex Approximation (SCA) method is proposed to decompose the initial problem into two sub-problems. Firstly, the UAV position is fixed to obtain the optimal values of other variables, and then the UAV position is optimized based on the solved variables. Finally, this iterative process continues until the algorithm convergences, and the optimal solution for the given problem is obtained. The simulation results indicate that the proposed algorithm exhibits good convergence. Compared to other benchmark solutions, the proposed approach performs optimally in maximizing computation bits. Full article
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<p>System model.</p>
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<p>Frame structure.</p>
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<p>The total number of computation bits for all the user versus the number of iterations.</p>
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<p>Optimal deployment position of UAV.</p>
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<p>Comparison of the number of computation bits for each user before and after optimizing the UAV position.</p>
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<p>The UAV transmit power versus the total number of computation bits for all users.</p>
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<p>The average number of computation bits per user versus the number of users.</p>
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<p>The total number of computation bits for all users versus UAV altitude.</p>
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<p>Computation bits versus the transmission power under different methods.</p>
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<p>Computation bits versus the length of time block under different methods.</p>
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28 pages, 19988 KiB  
Article
Performance Improvement of Wireless Power Transfer System for Sustainable EV Charging Using Dead-Time Integrated Pulse Density Modulation Approach
by Franklin John, Pongiannan Rakkiya Goundar Komarasamy, Narayanamoorthi Rajamanickam, Lukas Vavra, Jan Petrov and Vladimir Kral
Sustainability 2024, 16(16), 7045; https://doi.org/10.3390/su16167045 - 16 Aug 2024
Viewed by 548
Abstract
The recent developments in electric vehicle (EV) necessities the requirement of a human intervention free charging system for safe and reliable operation. Wireless power transfer (WPT) technology shows promising options to automate the charging process with user convenience. However, the operation of the [...] Read more.
The recent developments in electric vehicle (EV) necessities the requirement of a human intervention free charging system for safe and reliable operation. Wireless power transfer (WPT) technology shows promising options to automate the charging process with user convenience. However, the operation of the WPT system is designed to operate at a high-frequency (HF) range, which requires proper control and modulation technique to improve the performance of power electronic modules. This paper proposes a dead-time (DT) integrated Pulse Density Modulation (PDM) technique to provide better control with minimal voltage and current ripples at the switches. The proposed technique is investigated using a LCC-LCL compensated WPT system, which predominantly affects the high-frequency voltage and current ripples. The performance analysis is studied at different density conditions to explore the impact of the integrated PDM approach. Moreover, the PDM technique gives better control over the power transfer at different levels of load requirement. The simulation and experimental analysis was performed for a 3.7 kW WPT prototype test system under different modes of operation of the high-frequency power converters. Both the simulated and experimental results demonstrate that the proposed PDM technique effectively enhances the efficiency of the HF inverter while significantly reducing output current ripples, power dissipation and improving the overall WPT system efficiency to 92%, and leading to a reduction in the power loss in the range of 10% to 20%. This leads to improved overall system control and performance. Full article
(This article belongs to the Topic Advanced Electric Vehicle Technology, 2nd Volume)
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<p>Block diagram of WPT charger for EV.</p>
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<p>LCC-LCL compensation WPT circuit schematic.</p>
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<p>Equivalent high-frequency inverter circuit schematic of WPT as a H-bridge inverter.</p>
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<p>Concept waveform of PWM and PDM (<b>a</b>) without dead-time and (<b>b</b>) with dead-time.</p>
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<p>PDM generating logic diagram.</p>
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<p>(<b>a</b>) Operational waveforms of WPT system without the delay time; (<b>b</b>) current flow diagram for different states of WPT system.</p>
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<p>(<b>a</b>) Operational waveforms of WPT system considering <span class="html-italic">ϕ</span> = α ≥ 0 with the dead time and (<b>b</b>) operational states of WPT system with current flow.</p>
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<p>Formal output waveforms of the full bridge inverter when notch occurs.</p>
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<p>Comparison of harmonics f = 85 kHz, for PWM and PDM (with different pulse density d = 0.2, 0.5, 0.8) (<b>a</b>) without dead time and (<b>b</b>) with dead time.</p>
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<p>Equivalent circuit of a magnetic resonance wireless charger with LCC-LCL compensation topology.</p>
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<p>Experimental arrangements of WPT with Spartan 6.</p>
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<p>Simulation output wave forms of HF inverter WPT with PWM control for without dead time and with different dead times (500 ms, 1000 ms, 1500 ms, and 2000 ms).</p>
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<p>Simulation output wave forms of HF inverter WPT with PDM (D = 0.2) control for without dead time and with different dead times (500 ms, 1000 ms, 1500 ms, and 2000 ms).</p>
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<p>Simulation output wave forms of HF inverter WPT with PDM (D = 0.5) control for without dead time and with different dead times (500 ms, 1000 ms, 1500 ms, and 2000 ms).</p>
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<p>Simulation output wave forms of HF inverter WPT with PDM (d = 0.8) control for without dead time and with different dead times (0.5 µs,1.0 µs,1.5 µs, 2.0 µs).</p>
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<p>Graphical result analysis of WPT output parameters: (<b>a</b>) input DC voltage gain, (<b>b</b>) input DC voltage gain, (<b>c</b>) input AC voltage gain, (<b>d</b>) transconductance, (<b>e</b>) input DC power, (<b>f</b>) output DC load power, (<b>g</b>) receiver output power, and (<b>h</b>) receiver output power.</p>
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<p>(<b>a</b>) Experimental result of PWM-controlled HF inverter voltage and current without dead time; (<b>b</b>) switching pulse of PWM 50% duty cycle.</p>
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<p>Experimental results of HF inverter voltages and current with PWM control for different dead times: (<b>a</b>) td = 0.5 μs and (<b>b</b>) td = 1.0 μs. (<b>c</b>) td = 1.5 μs and (<b>d</b>) td = 2.0 μs.</p>
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<p>Experimental output of PDM HF inverter voltage and current without dead time; (<b>a</b>) Inverter Voltage and Current (<b>b</b>) Switching Pulses D = 0.5 (<b>c</b>). Inverter Voltage and Current PDM of D = 0.5 (<b>d</b>). PDM of D = 0.5 (<b>e</b>). Inverter Voltage and Current PDM of D = 0.8 (<b>f</b>) Switching Pulses D = 0.8.</p>
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<p>Experimental results of HF inverter voltages and current with PDM of d = 0.2 control for different dead times: (<b>a</b>) td = 0.5 μs and (<b>b</b>) td = 1.0 μs. (<b>c</b>) td = 1.5 μs and (<b>d</b>) td = 2.0 μs.</p>
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<p>Experimental results of HF inverter voltages and current with PDM of d = 0.5 control for different dead times: (<b>a</b>) td = 0.5 μs and (<b>b</b>) td = 1.0 μs. (<b>c</b>) td = 1.5 μs and (<b>d</b>) td = 2.0 μs.</p>
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<p>Experimental results of HF inverter voltages and current with PDM of d = 0.5 control for different dead times: (<b>a</b>) td = 0.5 μs and (<b>b</b>) td = 1.0 μs. (<b>c</b>) td = 1.5 μs and (<b>d</b>) td = 2.0 μs.</p>
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<p>Experimental results of HF inverter voltages and current with PDM of d = 0.8 control for different dead-times: (<b>a</b>) td = 0.5 μs and (<b>b</b>) td = 1.0 μs. (<b>c</b>) td = 1.5 μs and (<b>d</b>) td = 2.0 μs.</p>
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<p>The comparison experimental and simulation output current ripple with effect of different dead times for different PDM and PWM control.</p>
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18 pages, 4044 KiB  
Article
Multiple-Split Transmitting Coils for Stable Output Power in Wireless Power Transfer System with Variable Airgaps
by Youbin Jun, Jedok Kim, Sanguk Lee, Jaewon Rhee, Seongho Woo, Sungryul Huh, Changmin Lee, Seunghun Ryu, Hyunsoo Lee and Seungyoung Ahn
Energies 2024, 17(16), 4025; https://doi.org/10.3390/en17164025 - 14 Aug 2024
Viewed by 422
Abstract
In this paper, a tunable multi-split transmitting (TX) coil for a wireless power transfer (WPT) system that accommodates a wide range of distances between the TX and receiving (RX) coils is proposed. This method enables the WPT system to maintain a stable and [...] Read more.
In this paper, a tunable multi-split transmitting (TX) coil for a wireless power transfer (WPT) system that accommodates a wide range of distances between the TX and receiving (RX) coils is proposed. This method enables the WPT system to maintain a stable and consistent output power supply to the load, regardless of variations in coupling coefficients caused by changes in the distance between the TX and RX coils. The tunable multi-split TX coil can operate in various modes depending on how the wire connections between each TX coil are configured. This approach adjusts the inductance value of the TX coil for different conditions, using the same amount of coil as a conventional single-loop TX coil. The results show that by adjusting the TX coil to three different modes as the airgap varies from 50 mm to 250 mm, consistent output power is achieved with smaller variations in the input current and voltage compared to those in a conventional system. A conventional system requires an input voltage increase of approximately 529.64%, while the proposed system requires only a 42.93% increase. The proposed system enhances the power transfer capacity of the WPT system, particularly when operating in an over-coupling state. This approach provides a stable output power supply with a standardized and simplified TX coil structure. Full article
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<p>A typical IPT system, including an AC power supply, a power factor correction, a rectifier, an inverter, compensation circuits, a DC/DC converter, and the load.</p>
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<p>The variation of the output power and system efficiency depending on the change of <math display="inline"><semantics> <mrow> <msub> <mrow> <mi>k</mi> </mrow> <mrow> <mi>t</mi> <mi>x</mi> <mo>−</mo> <mi>r</mi> <mi>x</mi> </mrow> </msub> </mrow> </semantics></math> when the input voltage is fixed.</p>
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<p>The three operating modes of the proposed multi-split TX coil system using switching components, composed of a coupling system (TX and RX coil), a power source, an inverter, a compensation circuit for the TX and RX coils, a rectifier, and a DC load. The A and B nodes at the back of the inverter are connected to the respective A and B nodes of each mode.</p>
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<p>The equivalent circuit of a multi-split TX coil system with <math display="inline"><semantics> <mrow> <mi>n</mi> </mrow> </semantics></math> loops to calculate the capacitance values of each TX coil.</p>
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<p>The setup for the 3D EM solver and equivalent circuit for each mode: (<b>a</b>) mode 1, (<b>b</b>) mode 2, and (<b>c</b>) mode 3.</p>
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<p>The input voltage values of the conventional and proposed system with varying airgaps when the output power of the load is fixed at 200 W.</p>
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<p>Coil to coil efficiency, from the output power of the inverter to the input power of the rectifier.</p>
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<p>The experimental setup of the proposed system.</p>
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27 pages, 801 KiB  
Article
Maximizing Computation Rate for Sustainable Wireless-Powered MEC Network: An Efficient Dynamic Task Offloading Algorithm with User Assistance
by Huaiwen He, Feng Huang, Chenghao Zhou, Hong Shen and Yihong Yang
Mathematics 2024, 12(16), 2478; https://doi.org/10.3390/math12162478 - 10 Aug 2024
Viewed by 470
Abstract
In the Internet of Things (IoT) era, Mobile Edge Computing (MEC) significantly enhances the efficiency of smart devices but is limited by battery life issues. Wireless Power Transfer (WPT) addresses this issue by providing a stable energy supply. However, effectively managing overall energy [...] Read more.
In the Internet of Things (IoT) era, Mobile Edge Computing (MEC) significantly enhances the efficiency of smart devices but is limited by battery life issues. Wireless Power Transfer (WPT) addresses this issue by providing a stable energy supply. However, effectively managing overall energy consumption remains a critical and under-addressed aspect for ensuring the network’s sustainable operation and growth. In this paper, we consider a WPT-MEC network with user cooperation to migrate the double near–far effect for the mobile node (MD) far from the base station. We formulate the problem of maximizing long-term computation rates under a power consumption constraint as a multi-stage stochastic optimization (MSSO) problem. This approach is tailored for a sustainable WPT-MEC network, considering the dynamic and varying MEC network environment, including randomness in task arrivals and fluctuating channels. We introduce a virtual queue to transform the time-average energy constraint into a queue stability problem. Using the Lyapunov optimization technique, we decouple the stochastic optimization problem into a deterministic problem for each time slot, which can be further transformed into a convex problem and solved efficiently. Our proposed algorithm works efficiently online without requiring further system information. Extensive simulation results demonstrate that our proposed algorithm outperforms baseline schemes, achieving approximately 4% enhancement while maintain the queues stability. Rigorous mathematical analysis and experimental results show that our algorithm achieves O(1/V),O(V) trade-off between computation rate and queue stability. Full article
(This article belongs to the Section Mathematics and Computer Science)
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<p>System model of WPMEC network with user-assistance.</p>
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<p>An illustrative time division structure.</p>
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<p>Average task computation rate and average task queue length over time slots.</p>
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<p>Average task computation rates with different control parameter <span class="html-italic">V</span>.</p>
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<p>Task queue lengths with different control parameter <span class="html-italic">V</span>.</p>
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<p>Average task computation rate and task queue length with different energy constraint <math display="inline"><semantics> <mi>γ</mi> </semantics></math>.</p>
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<p>Convergence performance of energy consumption with different parameter <span class="html-italic">V</span>.</p>
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<p>Offloading power of FU and NU with different Bandwidth <span class="html-italic">W</span>.</p>
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<p>Average task computation rates in different schemes over time slots.</p>
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<p>Average computation rates in different schemes with different bandwidth <span class="html-italic">W</span>.</p>
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<p>Average computation rates in different schemes with different distances between FU and NU.</p>
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<p>Average computation rates in different schemes with different task arrival rates of FU.</p>
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13 pages, 5129 KiB  
Article
Fully Integrated Miniaturized Wireless Power Transfer Rectenna for Medical Applications Tested inside Biological Tissues
by Miguel Fernandez-Munoz, Mohamed Missous, Mohammadreza Sadeghi, Pablo Luis Lopez-Espi, Rocio Sanchez-Montero, Juan Antonio Martinez-Rojas and Efren Diez-Jimenez
Electronics 2024, 13(16), 3159; https://doi.org/10.3390/electronics13163159 - 10 Aug 2024
Viewed by 634
Abstract
This work presents the results of the characterization of two 1 × 5 mm2 miniaturized rectennas developed for medical applications. They have been designed for relatively high voltage and high-power applications, given the size of the rectennas. Both rectennas were tested in [...] Read more.
This work presents the results of the characterization of two 1 × 5 mm2 miniaturized rectennas developed for medical applications. They have been designed for relatively high voltage and high-power applications, given the size of the rectennas. Both rectennas were tested in open-air conditions and surrounded by pork fat and muscle tissues, whose properties are similar to those of the human body. The resonant frequencies of the rectennas were found, and the incident electric field on the rectennas tests was increased. The first chip showed a maximum output voltage of 5.29 V and a maximum output power of 0.056 mW, at 1.446 GHz, under an incident field on the rectenna of 340 V/m, and the second chip, 4.62 V and 4.27 mW, at 1.175 GHz, under 535 V/m. The second rectenna can provide an output power greater than 5 mW. The rectennas presented in this article are beyond the state of the art, as they can deliver about three times more power and voltage than those of similar dimensions reported in the literature. Based on the test results, the efficiency of the rectennas was analyzed at different locations of the human body, considering different thicknesses of tissues with high and low water content. Finally, potential applications are described in which the rectennas could power implantable medical devices or microsurgery tools, for example, pulmonary artery pressure monitors. Full article
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<p>(<b>a</b>) Microscopic view of the rectenna; (<b>b</b>) integration of the 1 × 5 mm<sup>2</sup> folded rectenna on a larger PCB; and (<b>c</b>) detail of microwelding by wire bonding.</p>
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<p>Test setup for the characterization of the rectennas in the semi-anechoic chamber. (1) Mast where the rectenna prototypes were attached, (2) mast where the transmitter antenna was attached, (3) switch and power amplifiers, (4) calibrated transmitting antenna, (5) electric field sensor, and (6) rectenna prototypes under test.</p>
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<p>Frequency sweep test procedure.</p>
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<p>(<b>a</b>) Frequency sweep test of the G2 rectenna; (<b>b</b>) frequency sweep test of the G3 rectenna.</p>
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<p>Power sweep test procedure.</p>
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<p>(<b>a</b>) Power sweep test at the resonant frequency of 1.46 GHz of the G2 rectenna; (<b>b</b>) power sweep test at the resonant frequency of 1.175 GHz of the G3 rectenna.</p>
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<p>(<b>a</b>) Cover design; (<b>b</b>) rectenna placed inside the 3D cover and wrapped with thin plastic sheet; (<b>c</b>) rectenna inserted in pork muscle; (<b>d</b>) rectenna inserted in pork fat; (<b>e</b>) test setup for the tests of the rectennas inside pork muscle; and (<b>f</b>) test setup for the tests of the rectennas inside pork fat.</p>
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<p>(<b>a</b>) Power sweep test at 785 MHz of the G2 rectenna surrounded by pork muscle tissues; (<b>b</b>) power sweep test at 1.28 GHz of the G2 rectenna surrounded by pork fat tissues.</p>
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<p>(<b>a</b>) Power sweep test at 785 MHz of the G3 rectenna surrounded by pork muscle tissues; (<b>b</b>) power sweep test at 1.05 GHz of the G3 rectenna surrounded by pork fat tissues.</p>
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17 pages, 6557 KiB  
Article
A Novel Hill Climbing-Golden Section Search Maximum Energy Efficiency Tracking Method for Wireless Power Transfer Systems in Unmanned Underwater Vehicles
by Yayu Ma, Bo Liang, Jiale Wang, Bo Cheng, Zhengchao Yan, Moyan Dong and Zhaoyong Mao
J. Mar. Sci. Eng. 2024, 12(8), 1336; https://doi.org/10.3390/jmse12081336 - 6 Aug 2024
Viewed by 711
Abstract
Efficiency has always been one of the most critical indicators for evaluating wireless power transfer (WPT) systems. To achieve fast maximum energy efficiency tracking (MEET), this paper provides an innovative control method utilizing the hill climbing-golden section search (HC-GSS) method of an LCC-S [...] Read more.
Efficiency has always been one of the most critical indicators for evaluating wireless power transfer (WPT) systems. To achieve fast maximum energy efficiency tracking (MEET), this paper provides an innovative control method utilizing the hill climbing-golden section search (HC-GSS) method of an LCC-S compensated WPT system. The receiver side includes a buck-boost converter that regulates the output current or voltage to meet output requirements. In the meantime, the buck-boost converter on the transmitter side is managed by the HC-GSS approach for MEET by minimizing the input power under the premise of output stability. Compared with the conventional P&O method, the HC-GSS method can eliminate the trade-off between the oscillation and convergence rate because it is designed for different system stages. In this WPT system, there is no need for direct communication between the transmitter and receiver. Therefore, the system is potentially cheaper to implement and does not suffer from annoying communication delays, which are prevalent in underwater environments for unmanned underwater vehicles’ (UUV) WPT systems. Both the simulation and experiment results show that this method can improve the efficiency of the WPT system without communication. The proposed method remains valid with coupler displacement as it does not include the mutual inductance of the system. Full article
(This article belongs to the Special Issue Advancements in New Concepts of Underwater Robotics)
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<p>Schematic diagram of the LCC-S compensated WPT system without communication.</p>
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<p>Simplified schematic diagram of LCC-S compensated WPT system.</p>
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<p>Mechanism for running the conventional P&amp;O MEET method in the WPT system.</p>
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<p>Flowchart of the conventional P&amp;O method for MEET in the WPT system.</p>
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<p>Relationship between WPT system efficiency and primary side buck-boost converter output voltage range.</p>
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<p>Optimal solution interval iterative process in improved hill climbing.</p>
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<p>Iterative calculation process of the golden section search method.</p>
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<p>Flowchart of the proposed HC-GSS method.</p>
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<p>Comparison of WPT system efficiency between without MEET and with the HC-GSS method.</p>
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<p>Comparison of the HC-GSS method and the conventional P&amp;O method: (<b>a</b>) The load resistance <span class="html-italic">R</span> = 5 Ω. (<b>b</b>) The load resistance <span class="html-italic">R</span> = 7.5 Ω. (<b>c</b>) The load resistance <span class="html-italic">R</span> = 10 Ω. (<b>d</b>) The load resistance <span class="html-italic">R</span> = 12.5 Ω. (<b>e</b>) The load resistance <span class="html-italic">R</span> = 15 Ω.</p>
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<p>Experimental prototype of the proposed WPT system.</p>
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<p>Output voltage regulation effect of secondary side buck-boost converter: (<b>a</b>) Increase the input voltage by 10 V. (<b>b</b>) Decrease the input voltage by 10 V.</p>
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<p>The MEET effects of the conventional P&amp;O method and the HC-GSS method under load conditions of <span class="html-italic">R</span> = 10 Ω: (<b>a</b>) MEET by conventional P&amp;O method, and (<b>b</b>) MEET by HC-GSS method.</p>
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10 pages, 2710 KiB  
Article
High-Efficiency 5G-Band Rectifier with Impedance Dispersion Compensation Network
by Yiyang Kong, Xue Bai, Leijun Xu and Jianfeng Chen
Electronics 2024, 13(16), 3105; https://doi.org/10.3390/electronics13163105 - 6 Aug 2024
Viewed by 597
Abstract
This paper proposes a microwave rectifier designed for the popular 5G band, featuring impedance dispersion compensation and a cross-type impedance matching network. The rectifier has an ultra-high power conversion efficiency. The compensation network employs two parallel transmission lines to counteract the nonlinear shift [...] Read more.
This paper proposes a microwave rectifier designed for the popular 5G band, featuring impedance dispersion compensation and a cross-type impedance matching network. The rectifier has an ultra-high power conversion efficiency. The compensation network employs two parallel transmission lines to counteract the nonlinear shift of the diode input impedance caused by frequency variation. Additionally, the cross-over impedance matching network enhances matching and minimizes losses. After rigorous theoretical analysis and simulation, the rectifier is fabricated. Experimental results show significant conversion efficiency in the 5G band (across 4–6.5 GHz). At an input power of 12 dBm, the rectifier achieves more than 60% efficiency between 4.8 and 6.4 GHz and more than 70% between 5.2 and 6.2 GHz, with a peak efficiency of 78.1%. Moreover, the rectifier maintains more than 50% efficiency over a wide input power range of 5 to 14 dBm. Full article
(This article belongs to the Special Issue Micro Energy Harvesters: Modelling, Design, and Applications)
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<p>Schematic diagram of the proposed rectifier with impedance dispersion compensation.</p>
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<p>Diode equivalent circuit model.</p>
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<p>Dispersion curve of <span class="html-italic">Z</span><sub>D</sub> with frequency.</p>
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<p>Impedance traces at (<b>a</b>) <span class="html-italic">p</span> = 12 dBm and (<b>b</b>) <span class="html-italic">p</span> = 9 dBm.</p>
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<p>(<b>a</b>) Proposed fabricated rectifier. (<b>b</b>) Photograph of the measuring setup.</p>
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<p>(<b>a</b>) Measured and simulated S11 of the rectifier for three power levels. (<b>b</b>) Measured and simulated RF-DC conversion efficiency versus frequency at three power levels. (<b>c</b>) Measured and simulated output voltage versus frequency at three power levels.</p>
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<p>(<b>a</b>) Efficiency variation curve measured at five different power levels. (<b>b</b>) Measured power conversion efficiency and output DC voltage of the rectifier circuit versus input power at different frequencies with load of 450 Ω.</p>
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43 pages, 11046 KiB  
Review
Review of Compensation Topologies Power Converters Coil Structure and Architectures for Dynamic Wireless Charging System for Electric Vehicle
by Narayanamoorthi Rajamanickam, Yuvaraja Shanmugam, Rahulkumar Jayaraman, Jan Petrov, Lukas Vavra and Radomir Gono
Energies 2024, 17(15), 3858; https://doi.org/10.3390/en17153858 - 5 Aug 2024
Viewed by 571
Abstract
The increasing demand for wireless power transfer (WPT) systems for electric vehicles (EVs) has necessitated advancements in charging solutions, with a particular focus on speed and efficiency. However, power transfer efficiency is the major concern in static and dynamic wireless charging (DWC) design. [...] Read more.
The increasing demand for wireless power transfer (WPT) systems for electric vehicles (EVs) has necessitated advancements in charging solutions, with a particular focus on speed and efficiency. However, power transfer efficiency is the major concern in static and dynamic wireless charging (DWC) design. Design consideration and improvements in all functional units are necessary for an increase in overall efficiency of the system. Recently, different research works have been presented regarding DWC at the power converter, coil structure and compensators. This paper provides a comprehensive review of power converters incorporating high-order compensation topologies, demonstrating their benefits in enhancing the DWC of EVs. The review also delves into the coupling coil structure and magnetic material architecture, pivotal in enhancing power transfer efficiency and capability. Moreover, the high-order compensation topologies used to effectively mitigate low-frequency ripple, improve voltage regulation, and facilitate a more compact and portable design are discussed. Furthermore, optimal coupling and different techniques to achieve maximum power transfer efficiency are discussed to boost magnetic interactions, thereby reducing power loss. Finally, this paper highlights the essential role of these components in developing efficient and reliable DWC systems for EVs, emphasizing their contribution to achieving high-power transfer efficiency and stability. Full article
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<p>Distribution of Bibliometric Analysis Documents.</p>
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<p>List of Co-authorships with Measures for the Top 10 Items for Author.</p>
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<p>List of Co-authorships with Measures for the Top 10 Items for Country.</p>
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<p>General Layout Structure of Keyword Search Analysis: (<b>a</b>) Density Plot; (<b>b</b>) Cluster Plot.</p>
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<p>WPT system with H-Bridge inverter.</p>
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<p>Resonance equivalent circuit: (<b>a</b>) LCL-based IPT system; (<b>b</b>) Equivalent circuit built on LCC; (<b>c</b>) Equivalent circuit built on SLC.</p>
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<p>WPT system using AC-to-AC matrix converter.</p>
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<p>Direct AC-to-AC converter.</p>
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<p>Class-E inverter Circuit diagram.</p>
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<p>WPT system with Class-E inverter.</p>
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<p>High-Efficiency WPT system with Class-E inverter.</p>
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<p>Simple circuit of compact high-efficiency topology.</p>
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<p>Resonance building blocks with LC components that operate with CC/CV sources and load in a generalized manner.</p>
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<p>A generalized block diagram of inductive coupling systems with an ideal T-block segregated from self-inductances.</p>
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<p>Four typical methods for compensating for and/or improving the efficiency of WPT systems.</p>
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<p>Components of a DIPT device with a single lengthy coil track.</p>
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<p>In a DIPT system, single transmitting wire tracks are used: (<b>a</b>) U-type, (<b>b</b>) E-type, (<b>c</b>) I-type, (<b>d</b>) S-type, (<b>e</b>) ultra-thin S-type, and (<b>f</b>) cross-segmented track (X-type).</p>
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<p>Sectionalized long transmission track configurations include (<b>a</b>) centralized switching, (<b>b</b>) dispersed switching, and (<b>c</b>) crossed-segmented switching.</p>
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<p>Sectionalized long transmission track configurations include (<b>a</b>) centralized switching, (<b>b</b>) dispersed switching, and (<b>c</b>) crossed-segmented switching.</p>
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<p>Supply options for the DIPT system’s segmented transmitter: (<b>A</b>) utilizing a common dc-bus and (<b>B</b>) using a universal HF ac-bus.</p>
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<p>Arrangement of reflexive segmentation.</p>
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<p>Additional supply solutions for DIPT system segmented transmitters that allow control of individual charging segments: (<b>A</b>) using a common HF inverter with a long magnetic route and (<b>B</b>) utilizing a common HF inverter with transmitter segment series connection.</p>
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<p>Schematics of (<b>a</b>) doubled coupled system and (<b>b</b>) intermediate coupler circuit (ICC).</p>
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<p>Implementation of receiver pad in DIPT system: (<b>A</b>) single pad and (<b>B</b>) multiple pads.</p>
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<p>Research progress and a brief history of soft magnetic materials.</p>
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<p>Effect of aluminum shielding on magnetic field density values.</p>
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<p>HBSE flowchart.</p>
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